FIELD
[0001]
Embodiments of the invention relate to wireless communications, and more particularly, to an electronic device and a wireless communication method for wireless communication.
Background technique
[0002]
When the fast varying channel environment (e.g., high-speed rail), the Doppler effect due to relative movement between the sending and receiving end due to affect the performance of the wireless communication system. Further, in a wireless cellular mobile communication system, in order to suppress the carrier frequency offset due to the inconsistency of the frequency generated by the transceiver, usually automatic frequency offset calibration to adjust the frequency of the receiver local oscillator by measuring the frequency of the received signal, thereby making the carrier frequency of the local oscillator frequency and the received synchronization signal. When the fast varying channel environment, because the transceiver of the frequency produced inconsistent and Doppler frequency offset generated by the relative movement between the sending and receiving end impact mode frequency shift of the received signal are similar. Thus at the receiving end by an automatic frequency estimated frequency offset parameter calibration technique essentially comprises both a transceiver of the frequency due to inconsistencies resulting Doppler frequency offset also includes generating a relative movement between the sending and receiving end of the frequency shift.
[0003]
SUMMARY
[0004]
Typically, the Doppler effect in order to reduce the signal receiving end, the transmit end to the signal frequency of the transmission signal preprocessing parameters of the received signal by the Doppler estimation. At the transmitting end, when the frequency of the transmission signal preprocessing, the need to use the Doppler shift parameter is not due to the carrier frequency offset of the frequency transceiver inconsistent generated. Under normal circumstances, the receiving end a frequency difference between the oscillator and the oscillator is transmitted unavoidably present. Thus the related art when the pre-frequency transmission signal, because the frequency offset of the frequency by the transceivers to produce inconsistent and Doppler produce relative movement between the sending and receiving end can not be distinguished from the frequency shift, and thus can not be suppressed due to the opposite ends between the transceiver Effect of the mobile receiver performance Doppler frequency shift produced.
[0005]
On the other hand, the base station transmits a signal using the wireless network coverage mode in a wireless cellular system. For the Doppler effect not only on the relative speed of movement between the sending and receiving end, the received signal is also related to the angle of arrival. When the mobile station moves to the vicinity of the base station and the mobile station performs handover between two base stations, the Doppler frequency change is very large. This related art is one of the main variable in the fast handover failure and call drop occurs a channel environment.
[0006]
It gives a brief overview of embodiments of the invention hereinafter, in order to provide a basic understanding of some aspects of the invention. It should be understood that the following summary is not an exhaustive overview of the invention. It is not intended to identify key or critical part of the invention, nor is it intended to limit the scope of the present invention. Its sole purpose is to present some concepts in a simplified form, as a prelude to the more detailed description that is discussed later.
[0007]
According to one aspect of the present invention, an electronic apparatus for wireless communication includes one or more processor. The processor is configured to: receive signals on the plurality of antennas are spatially filtered; the filtered signal based on the spatial frequency offset is estimated respective antennas corresponding to the received signal; and the frequency offset in accordance with the estimated spatial filter parameters estimated Doppler created by the relative motion between the sending and receiving end the received signal and the frequency shift of the frequency by the transceivers inconsistent generated carrier frequency offset; and pretreated according to the estimated frequency Doppler shift of the antenna signal transmission and / or to perform control with the estimated Doppler shift information related to the feedback signal receiving end of the transmission.
[0008]
According to another aspect of the present invention, a wireless communication method, comprising: receiving a plurality of antennas signals are spatially filtered; spatial filter based on the signals of the respective antennas corresponding to the estimated frequency offset of a received signal; based on the estimated and frequency offset of spatial filter parameters, generated by the estimated Doppler relative movement between the sending and receiving end of the signal received by the transceiver and the frequency shift of the frequency of the carrier frequency offset produced inconsistent; and based on the estimated Doppler shift of the antenna the pre-transmission signal frequency, and / or controls to the estimated Doppler shift related to the transmitted information back to the end of the received signal.
[0009]
The solution according to the present embodiment of the invention help to improve the throughput performance of a wireless communication system under varying channel environment fast.
BRIEF DESCRIPTION
[0010]
The present invention may be better understood by reference to the following description in conjunction with the accompanying drawings given, in which the same or similar reference numerals in the drawings to refer to the same or like parts. The drawings together with the detailed description are included in a part of the present specification and form of this specification, and serve to further illustrate the embodiments and explain the principles and advantages of the present invention is preferably present invention. In the drawings:
[0011]
FIG. 1 is a block diagram showing a configuration example of electronic equipment for wireless communication according to one embodiment of the present invention;
[0012]
FIG 2 is a block diagram illustrating a configuration example of electronic equipment for wireless communication according to another embodiment;
[0013]
FIG 3 is a flowchart illustrating an example of a process of the wireless communication method according to one embodiment of the present invention;
[0014]
FIG 4 is a flowchart of another wireless communication method of an embodiment of an example of the process illustrated;
[0015]
FIG 5 is a flowchart illustrating an example of a process of the wireless communication method of still another embodiment;
[0016]
FIG 6 is a diagram illustrating a configuration example of a user apparatus according to an exemplary embodiment of a block diagram;
[0017]
FIG 7 is a block diagram illustrating a configuration example of a base station according to one embodiment of the exemplary embodiment;
[0018]
FIG 8 is a schematic diagram for explaining the embodiment of the information interaction process performed between the base station and the user equipment in one exemplary embodiment;
[0019]
FIG 9 is a block diagram showing a configuration example of electronic equipment for wireless communication according to one embodiment of the present invention;
[0020]
FIG 10 is a block diagram of an exemplary configuration of a computer implemented method and apparatus illustrating the present disclosure;
[0021]
FIG 11 is a block diagram illustrating an example of a schematic configuration of a smart phone art shows the present disclosure may be applied;
[0022]
FIG 12 is a block diagram illustrating an example of an eNB according to the present disclosure may be applied techniques (eNB) is a schematic configuration; and
[0023]
Schematic block diagram of an exemplary configuration of a car navigation device 13 of FIG technique may be applicable to the present disclosure.
detailed description
[0024]
It will now be described with reference to the accompanying drawings of embodiments of the present invention. Elements and features of the elements and features described in one figure or one embodiment of the present invention may be illustrated embodiment with one or more other drawings or embodiments described combination. It should be noted that for purposes of clarity, the drawings and the description is omitted irrelevant to the present invention, shown and described are known to those of ordinary skill in the components and processes.
[0025]
, An electronic equipment for wireless communication according to one embodiment 100 includes one or more processors 110, a processor 110 includes a filtering unit 111 in FIG. 1, a first estimation unit 113, second estimation unit 115 and the pre- processing / control unit 117.
[0026]
It is noted that, although the figures shown in a dashed box to separate the filter unit 111 in the processor 110, a first estimating unit 113, estimation unit 115 and the second pre-processing / control unit 117, it should be understood that these the functional unit as a whole may be implemented by the processor 110, and not necessarily by the processor 110 in the separate components to achieve practical. Further, although to a block in FIG processor 110 is shown, however, the electronic device 100 may include a plurality of processors, the filtering unit 111 may be a first estimation unit 113, estimation unit 115 and the second pre-processing / control unit 117 function across multiple processors so that multiple processors cooperating to perform these functions.
[0027]
The filtering unit 111 is configured to receive a plurality of antennas signals are spatially filtered.
[0028]
Specifically, a spatial filtering carried out from a plurality of antennas and the reception signal may be expressed as:
[0029]
Equation 1 r = Fy
[0030]
Wherein, y is a length of N received signal vector, r is the length of the filtered signal vector of N, F is the size of N × N spatial filter matrix elements on the k-th row of the spatial filter matrix corresponding to the k-th spatial filter coefficients, a length of N. Each spatial filter coefficients may determine the minimum wavenumber spectrum equivalent method such as by expansion.
[0031]
It is noted that, for the purpose of spatial filter herein is for the Doppler in the subsequent processing of the relative movement between the receiving and sending ends generated by the transceiver and the frequency shift of the frequency produced inconsistent joint carrier frequency offset estimation signal providing the necessary dimensions .
[0032]
A first estimation unit 113 is configured based on the spatial filter for each antenna signal corresponding to the estimated frequency offset of the received signal.
[0033]
A first estimation unit 113 may estimate frequency offset of the various ways known in the art employed. For example, according to one embodiment, the first estimation unit 113 by a method based on the estimated training sequence estimation or blind methods based on statistical information signal to estimate the frequency offset corresponding to the received signal, but the present invention is not limited thereto.
[0034]
It is noted that the first estimation unit 113 estimates the frequency offset component may comprise a Doppler frequency shift resulting from the relative movement between the sending and receiving end of the transceiver and a signal of the frequency of the carrier frequency offset produced inconsistent component. As described above, according to the related art, the two can not be distinguished on the frequency offset component, and sometimes is simply the sum of these two frequencies is approximately offset component as Doppler shift (e.g., referred to as a multi-equivalent Doppler shift) for subsequent processing. While the embodiment of the present invention enables a joint estimation of the frequency offset of the two components, i.e., it can be separately estimated carrier frequency offset and Doppler shift.
[0035]
The second estimation unit 115 to unit 113 is configured to estimate the frequency offset and the spatial filtering means for filtering parameters 111 for estimating a first Doppler estimation generated by the relative movement between the sending and receiving end of the reception signal a frequency shift and inconsistency of the frequency generated by the transceiver carrier offset.
[0036]
Next, with reference to specific exemplary embodiment described and estimating a first estimation unit 113, second estimation unit 115 for processing. It is understood that the invention is not limited to the specific details of the following examples design.
[0037]
Suppose N is the receiving end antennas, respectively, the filtering unit 111 using the spatial filter of the N respective antennas reception signals are spatially filtered. A first estimation unit 113 may obtain N frequency offset estimation parameter, expressed as a filtered signal 111 in accordance with the filter unit wherein the n-th spatial filter filters the signal by the estimated frequency offset. It should be noted that, although a represents a respective frequency offset of the received signal by the first estimating unit 113 estimated, the frequency offset includes not only a Doppler shift component, also contains a component carrier frequency offset (or may be herein understood to correspond to the aforementioned equivalent Doppler shift).
[0038]
As described above, the first training sequence estimation may be performed when the estimation unit 113 based autocorrelation or cross-correlation estimation algorithm may be employed carrier frequency offset estimator. The estimated parameters and the transceiver is not only inconsistent ends generated frequency carrier frequency offset F [Delta] and the Doppler generated by the relative movement between the sending and receiving end of the signal frequency shift F D , but also on the n-th with the parameters related to spatial filter, It can be expressed as:
[0039]
[0040]
Wherein, [theta] R & lt e.g. moving direction angle of the mobile terminal to the signal receiving end, by the direction of the n-th spatial filter parameter determining the angle, specifically calculated by the following formula
[0041]
[0042]
Where λ is the wavelength, n-th spatial filter corresponding to the mean wave number, namely:
[0043]
[0044]
Where S n (K) according to the shape of the antenna array and the n-th spatial filter parameters, the angle of its corresponding spectrum [rho] n ([theta]) according to the following equation to calculate the corresponding wave number spectra obtained, i.e.,
[0045]
[0046]
其中k 0 = 2π / λ.
[0047]
Since it is determined by the spatial filter parameters, when determining spatial filter parameters, as known parameters. Thus in Equation 2 only two variables to be solved, i.e., F [Delta] and F D .
[0048]
In other words, according to one embodiment, the second estimation unit 115 may frequency shift is the Doppler frequency shift F D and F frequency offset [Delta] a relationship of a linear combination of estimated Doppler shift F D and the carrier frequency partial f delta . Wherein, the relationship may be a linear combination of the filtered signal to noise ratio in accordance with the respective plurality of antennas by spatial, for each direction of the spatial filter corner angle θ relative movement of the receiver and sender and the reception signal in the direction R determined.
[0049]
Further, Equation 2 can be constructed of a binary N-dimensional signal vector F D , and the weighted least squares method may be employed for conducting a binary parameter (F [Delta] and F D ) Joint Estimation. Methods as below:
[0050]
[f Δ f d]＝(A TwA) -1Α Twf d 等式6
[0051]
Where A is an observation matrix, w is a weighting matrix estimate. Objective weighting matrix is ​​due to the N spatial filter output signal does not necessarily contain the useful signal.
[0052]
The observation matrix A may be expressed as:
[0053]
[0054]
Weighting matrix w may be expressed as:
[0055]
V = W -1 Equation 8
[0056]
Wherein V is F D estimation error matrix, a diagonal matrix.
[0057]
In other words, according to one embodiment, the second estimation unit 115 and the observation matrix may be utilized to calculate the weighting matrix is the Doppler frequency shift f d and f carrier frequency offset [Delta] estimates, wherein the direction angle of the observation matrix , and the direction angle [theta] R & lt relevant. Further, the matrix may be observed depending on the direction angle angle θ and direction R determined in advance.
[0058]
On the other hand, the weighting matrix may be related to noise ratio by the spatial filtered signal.
[0059]
For example, in Equation 8 estimation error matrix V n-th diagonal element of V n may be expressed as:
[0060]
[0061]
Where L is the length of the training sequence period, T S is the symbol period length, the SNR n for the n-th through the spatial filter signal to noise ratio after filtering. May be calculated by the following formula the SNR n- :
[0062]
[0063]
Wherein the SNR ' n is the estimated autocorrelation n-th spatial filter filters the signal to noise ratio, which can be expressed as:
[0064]
[0065]
Wherein R & lt n (I) for the n-th spatial filter filters the signal, K is the length of the training sequence. Since the weighting matrix w need to use the received signal r (i) the spatial filter to be calculated, and therefore the need to calculate the weighting matrix values online.
[0066]
In other words, according to one embodiment, a weighting matrix based on the estimated signal to noise ratio of the frame-by Spatial Filtering determined.
[0067]
Further, in the above-described exemplary embodiments, it may be estimated by a weighted least squares Doppler shift F D and F frequency offset [Delta] , wherein the weighted signal to noise ratio of the filtered signal over a plurality of antennas of the respective airspace. Wherein, for example, the SNR can be estimated by the autocorrelation method.
[0068]
By using the weighting matrix, it helps to improve the robustness of the algorithm to jointly estimate the estimation accuracy and under non-ideal conditions.
[0069]
Further, according to one embodiment, the filtering unit 111, a first estimation unit 113 and the second estimation unit 115 may be configured to perform the above-described process for the received signal frame by frame, to estimate the Doppler shift and carrier frequency offset.
[0070]
The electronic device according to an embodiment of the present invention may utilize the estimated carrier frequency offset and Doppler shift for different subsequent processing.
[0071]
For example, pre-processing / control unit 117 may be configured to perform pre-processing based on the estimated frequency Doppler shift of the antenna signal transmission.
[0072]
More specifically, the frequency of pre-treatment may comprise: using the respective different spatial directions different Doppler shift estimate pretreatment, and using the estimated received signal to noise ratio of each spatial transmission signal obtained by weighting.
[0073]
Hereinafter given by way of example follow the frequency transmission signal preprocessing based on the estimated Doppler shift based on the received signal. It is understood that the invention is not limited to the specific details of the following examples.
[0074]
When f is obtained by joint estimation of Δ and f D , the pre-processing / control unit 117 may perform preprocessing on a transmission signal frequency obtained from a received signal using the estimated Doppler shift, and each spatial filter parameters, i.e.,
[0075]
[0076]
Wherein, x (t) is the transmission information signal, E n (T) to transmit a signal in the n-th spatially corresponding spatial filter, A (n, 2) row of the n-th row on the second observation matrix A Elements.
[0077]
In other words, when the frequency of the transmission signal preprocessing can be employed for various different spatial directions different Doppler estimation parameters pretreatment. Further, it may also be employed received SNR of each spatial parameter estimation signal obtained by weighting the transmission signal to the adaptive varying wireless channel environment.
[0078]
Alternatively or additionally, pre-processing / control unit 117 may also be configured to control the estimated Doppler shift information about the feedback signal transmitted to the corresponding terminal.
[0079]
The received signal to estimate the Doppler parameters using the receiving end, then the parameters of the feedback way back to the sender may be referred to as closed-loop control Doppler. Sending end receives the parameter, the signal transmission in the next process, this parameter may be used to pre-process the signals transmitted, in order to achieve lower receiving end receives the signal Doppler effect.
[0080]
Further, the signal receiving end may also use the strongest signal to noise ratio corresponding to the filter after the estimated Doppler shift select each spatial filter, the feedback filter corresponding to the Doppler parameters to the sender, to implement a closed loop Doppler control. Doppler parameters, for example, reported F D A (p, 2), where p is the index of the spatial filter filters the signal to noise ratio corresponding to the strongest signal.
[0081]
In other words, with the estimated Doppler shift may also contain information about the spatial filtering by the spatial filter in the direction of the highest SNR signal, a signal corresponding to the angle.
[0082]
The feedback information, and may transmit a signal corresponding to the frequency of the pretreatment, for example with different Doppler estimation parameters pretreated different spatial directions from respective opposite ends of the communication of the communication apparatus of the present embodiment of the invention, , and it may also be a transmission signal using weighting parameters of the received signal to noise ratio of each spatial estimation obtained.
[0083]
On the other hand, the electronic device according to the present invention may be implemented on the frequency of the local frequency generator is calibrated using the estimated carrier frequency offset. Next, with reference to FIG. 2 illustrates such an embodiment.
[0084]
2, the electronic device according to an embodiment for wireless communication 200 includes one or more processors 200, the processor 200 211, a filtering unit comprises a first estimation unit 213, second estimation unit 215, pre- processing / control unit 217 and a calibration unit 219. Wherein the filtering unit 211, a first estimating unit 213, estimation unit 215 and the second pre-processing / control unit 217, respectively, the filtering unit 111 previously described with reference to FIG. 1, a first estimation unit 113, estimation unit 115 and the second pre- / similar to the control unit 117, detailed description thereof is omitted here.
[0085]
The calibration unit 219 is configured to offset the frequency of the local frequency generator is calibrated according to a second estimation unit 215 estimates carrier. Thereby, possible to reduce the carrier frequency offset of the frequency due to the inconsistency between the transceiver caused.
[0086]
It is noted that the electronic device for wireless communication 100 and 200 may operate as a user equipment (UE). In this case, for example, which may signal or a downlink from a base station from other user equipment (e.g. in the case of direct communication between devices) of the above process signals. However, the present invention is not limited thereto, embodiments of the present invention may be applied to estimate the uplink signal, for example, a Doppler frequency shift from the user equipment and the base station side frequency offset, and the corresponding processing based on the estimation result.
[0087]
At least one signal using a plurality of spatial filters according to embodiments of the present invention, the filter, and Doppler frequency offset generated by the relative movement between the sending and receiving end of the frequency by the transceivers to produce inconsistent joint estimation of the frequency shift. When the transmission signal, obtained from a received signal using the estimated frequency offset and Doppler shift parameters and filter parameters of each spatial frequency of the transmission signal preprocessing improves the system throughput performance in the fast varying channel environment.
[0088]
In particular, the Doppler effect is suppression signal receiving end in the case of the fast varying channel environment, in the related art can not be offset by the presence of the frequency transceiver inconsistent generated. At least one embodiment of the present invention by the received signal spatial filter using the weighted least squares method for conducting a binary parameter (F [Delta] and F D ) joint estimation and spatial filter combined with the corresponding parameters of the transmission signal frequency pretreatment to inhibit the signal receiving end of the Doppler effect. Effects of each of the various embodiments of the present invention comprises one of the following:
[0089]
1) solves the problem of Doppler shift parameters related art in the fast varying channel environment at, for example, in particular not track the rapid changes in the user equipment and a base station handover occurs close. Improving system performance when approaching the base station and the handover occurs. Thereby solving the under fast varying channel environment, frequent dropped calls because the system can not track the rapid changes in the Doppler shift caused parameters and handover failures.
[0090]
2) to solve the related art in the fast varying channel environment, when there are inconsistencies oscillator frequency of transmitter and receiver can not be effective in inhibiting the frequency receiving end pretreatment Doppler effect problem.
[0091]
3) When the transmission signal by combining the various spatial filter parameters at various spatial frequencies pretreatment solve the related art when the terminal with two and more than two base transceiver stations at the same time the frequency of the problem is difficult to perform communication pretreatment.

Claims
[Claim 1]
An electronic device for wireless communications, comprising: one or more processors configured to receive signals of the plurality of antennas are spatially filtered; estimating a frequency corresponding to the reception signal based on the spatial filtering of the signals of the respective antennas offset; based on the estimated frequency offset and the spatial filter parameter is estimated between the Doppler signal received by the transceiver end of the relative movement and the frequency shift of the frequency by the transceivers inconsistent generated carrier frequency offset; and pretreatment of the transmission signal frequency of the antenna based on the estimated Doppler shift, and / or controls to shift information associated with the estimated Doppler feedback to the transmitting end of the received signal.
[Claim 2]
The electronic apparatus according to claim 1, wherein, according to the frequency offset is estimated and the relationship of the Doppler shift of the carrier frequency offset of a linear combination of the Doppler shift of said carrier and frequency offset.
[Claim 3]
The electronic apparatus according to claim 2, wherein, by a weighted least squares estimation of the Doppler shift and the frequency offset, which the SNR of the filtered signals according to a plurality of antennas via respective airspace said weighting.
[Claim 4]
The electronic apparatus according to claim 3, wherein the relationship is a linear combination of the filtered signal to noise ratio of each of the plurality of antennas by spatial direction for each of said angular spatial filter and said received signal end of the transceiver relative motion direction angle [theta] R & lt determined.
[Claim 5]
The electronic apparatus according to claim 4, wherein the observation matrix using a weighting matrix to calculate and estimate the Doppler shift and the carrier frequency offset, wherein the observation matrix the directional angle and the said direction angle [theta] R & lt related to the weighting of the signal to noise ratio by the spatial filter matrix concerned.
[Claim 6]
The electronic device according to claim 5, wherein said matrix is based on the observation angle direction angle θ and the direction R determined in advance.
[Claim 7]
The electronic device according to claim 5, wherein the weighting matrix is ​​estimated based on the signal to noise ratio determined from frame to frame.
[Claim 8]
The electronic apparatus according to claim 1, wherein, by estimating method based on training sequence estimation or blind methods based on statistical information signal to estimate the frequency offset.
[Claim 9]
The electronic apparatus according to claim 3, wherein the signal to noise ratio estimated by the autocorrelation method.
[Claim 10]
The electronic apparatus according to claim 1, wherein the processor is configured to estimate for the received signal frame by frame and the Doppler shift of the carrier frequency offset.
[Claim 11]
The electronic apparatus according to claim 1, wherein said frequency pre-processing includes: using respective different spatial directions for different Doppler shift estimate pretreatment and the use of spatial signal to noise respective received signal estimate obtained weight ratio of a transmission signal.
[Claim 12]
The electronic device according to any one of 1-11 claims, wherein the processor is further configured to: calibrate the frequency of the local frequency generator in accordance with the estimated carrier frequency offset.
[Claim 13]
The electronic apparatus according to claim 1, wherein, with the estimated Doppler shift information further contains the following information: spatial filtering by the spatial filter in the direction of the highest signal to noise ratio of the signal corresponding to the angle.
[Claim 14]
The electronic device according to any one of 1-11 claims, wherein the working electronic device is a user equipment.
[Claim 15]
A radio communication method, comprising: a plurality of antennas for receiving signals separately spatial filtering; spatial filter based on the signals of the respective antennas corresponding to the estimated frequency offset of a received signal; based on the estimated frequency offset and the spatial filter parameters generated by Doppler estimation and received between the end of the reception signal a frequency shift and relative motion of the frequency by the transceivers inconsistent generated carrier frequency offset; and a frequency shift of the transmitting antennas based on the estimated Doppler preprocessing the signal frequency, and / or controls to shift information associated with the estimated Doppler feedback to the transmitting end of the received signal.
[Claim 16]
The method according to claim 15, wherein the frequency offset is based on the relationship of the Doppler shift of the carrier frequency offset and a linear combination of the estimated Doppler shift of the carrier frequency and partial.
[Claim 17]
The method according to claim 16, wherein, by a weighted least squares estimation of the Doppler shift and the carrier frequency offset, wherein the SNR of the filtered signals according to a plurality of antennas by each of the airspace weighted.
[Claim 18]
The method according to claim 17, wherein the relationship is a linear combination of the filtered signal to noise ratio of each of the plurality of antennas by spatial direction for each of said spatial filtering angle and a transceiver of the received signal end relative movement direction angle [theta] R & lt determined.
[Claim 19]
The method according to claim 18, wherein the observation matrix using a weighting matrix to calculate and estimate the frequency shift and the Doppler frequency offset, wherein the observation matrix the directional angle and the direction angle [theta] R & lt related to the weighting of the signal to noise ratio by the spatial filter matrix concerned.
[Claim 20]
The method according to claim 19, wherein said matrix is based on the observation angle direction angle θ and the direction R determined in advance.
[Claim 21]
The method according to claim 19, wherein the weighting matrix is ​​estimated based on the signal to noise ratio determined from frame to frame.
[Claim 22]
The method according to claim 15, wherein, by a method based on the training sequence estimation or blind estimation signal based on statistical information to estimate the frequency offset.
[Claim 23]
The method according to claim 17, wherein the signal to noise ratio estimated by the autocorrelation method.
[Claim 24]
The method according to claim 15, wherein said estimated frequency shift and the Doppler frequency offset for the received signal frame by frame.
[Claim 25]
The method according to claim 15, wherein said frequency pre-processing includes: using respective different spatial directions for different Doppler shift estimate pretreatment, and using the estimated received signal to noise ratio of each spatial obtained weighting the transmission signal.
[Claim 26]
The method according to any one of claims 15-25 claims, further comprising: calibrating the frequency of the local frequency generator in accordance with the estimated carrier frequency offset.
[Claim 27]
The method according to claim 15, wherein, with the estimated Doppler shift information further contains the following information: spatial filtering by the spatial filter in the direction of the highest signal to noise ratio of the signal corresponding to the angle.
[Claim 28]
15 The method of any one of claim 25, further comprising: sending, by the end of the pre-frequency signal in accordance with the subsequent transmission to the estimated Doppler shift related information