The present invention relates to the field of array antennas and in particular active antennas. It applies in particular radars, electronic warfare systems (such as radar detectors and radar jammers) as well as communication systems or other multifunction systems.
A said array antenna comprises a plurality of antennas may be of the planar type, ie the printed circuit type often called patch antennas. Technology planar antennas allows for very thick antennas instructions by making the radiating elements by etching metal patterns on a dielectric layer provided with a metallic ground plane on the rear panel. This technology leads to phased array antennas very compact guidelines easier to perform and less expensive than the Vivaldi type antennas.
An active antenna conventionally comprises a set of antenna elements each comprising a substantially planar radiating element coupled to a transmit / receive module (or T / R circuit to "Transmit / Receive circuit" in English). Each transmission / reception circuit is connected to an excitation point. Each transmitting / receiving circuit comprises, in the electronic warfare applications a power amplifying chain which amplifies an excitation signal received centralized signal generating an electronic and excites the excitation point and a low noise amplifying chain which amplifies, in reception mode, a reception signal of low level, received by the radiating element at the point of
This type of array antennas has a number of disadvantages. Indeed, the low noise amplification chains have different optimum input impedances of the optimum output impedances of the power amplifying channels. Usually, the impedance of the excitation point is set to 50 Ohms, as instrumentation equipment are planned for this impedance. This is not however the optimal impedance for the HPA power amplifiers (in reference to the English expression "High Power Amplifier") or for low noise amplifiers LNA (referring to the term Anglo
Saxon "Low Noise Amplifier"). To overcome this drawback, it is customary to have an impedance transformer at the output of the power amplifying unit and the input of the low noise amplification chain. This transformer leads to less efficient in transmission, resulting in significant energy losses at the origin of heat dissipation. It also leads to a noise factor NF worse reception (NF for Noise Figure in English), the signal to noise ratio of the received signal is degraded.
It may be necessary to transmit signals having different powers by means of a single array antenna. signals, said radar may for example transmit, high power and having a spreading band narrow frequency (narrowband-type is 10 to 20% of center frequency) and signals, telecommunication, or radar jamming having a spread in wide frequency band (broadband type, the spreading band up to three octaves) and a lower power. These signals may be transmitted simultaneously or sequentially.

However, this solution has drawbacks. This type of signal summer transformer integrated upstream of the radiator in the MMIC, is bulky and leads to significant energy losses. To limit heating of the integrated circuit, it is essential to cool that requires a specific and involves a significant energy consumption equipment.

An object of the invention is to provide a planar radiating device that achieves an antenna wherein at least one of the aforementioned disadvantages is reduced.

To this end, the invention relates to an antenna element comprising a planar radiating device comprising a substantially planar radiating element and a transmit and / or receive circuit

comprising at least an amplification chain of a first type and at least one amplification chain of a second type, of a first set each amplifier chain of the first type being coupled to at least one excitation point at least one excitation of the radiating element point and each amplification chain of the second type being coupled to at least one point of a second set of excitation points of the radiating element, the points of excitation of the first and second assembly being distinct and the amplification system of the first type being different from the amplification chain of the second type so that they have different amplification properties.

Advantageously, the excitation points of the first set and the second set having different impedances.

According to a first embodiment of the invention, the antenna comprises a transmitting and receiving circuit, said transmitting and receiving circuit comprising:

- at least one own transmit amplifier chain to provide signals for energizing the radiating element, each transmit amplifier chain being coupled to at least one point of the first set of at least one point excitation of said radiating element;

- at least one own reception amplification system for amplifying signals from the radiating element, each receiving amplifier chain being coupled to at least one point of the second set of at least one excitation point of said element beaming.

Advantageously, the excitation points are positioned and coupled to the respective amplification channels such that each amplification chain is loaded substantially by its optimal impedance, the impedance loaded onto each amplification chain being the impedance of the chain formed by the radiating device coupled to the amplification chain and each supply line connecting the radiating device to the amplification chain.

Advantageously, at least one emission amplification chain coupled to a point or two points in the first set has an output impedance that is substantially conjugate with an impedance of the radiating device presented to said transmit amplifier chain , said point or between two points of the first coupled set (s); and / or at least one receiving amplifier chain coupled to a point or two

points of the first assembly has an output impedance substantially conjugate with an impedance of the radiating device presented to said reception amplification chain or said point between the two points of the second set coupled (s).

According to a second embodiment of the invention, the antenna element comprises a transmitting circuit, the transmitting circuit comprising:

- at least a said transmit amplifier chain high own power providing signals for energizing the radiating element, each high power transmit amplifier chain being coupled to at least one point of the first set at least one excitation point of said radiating element;

- at least a second said emission amplifier chain low power, lower than the first power amplifying power chain, adapted to deliver signals to excite the radiating element, each channel of amplification 'low power transmission being coupled to at least one point of the second set of at least one excitation point of said radiating element.

Advantageously, the excitation points are positioned and coupled to each transmit amplifier chain high power so that each high power amplifier chain is loaded substantially by its optimal impedance, the impedance loaded onto each chain amplifying high power being the impedance of the chain formed by the radiating device coupled to the amplifier and each feed line coupling the radiating device to the high power emission amplification system chain.

Advantageously, at least one high power emission amplification chain coupled to a point or two points in the first set has an output impedance that is substantially conjugate with an impedance of the radiating device presented in said amplifier chain transmitting said point or between two points of the first set.

Both embodiments may include one or more of the following characteristics, taken in isolation or in all technically possible combinations:

- the impedance of each of the first set of excitation point is less than the impedance of each excitation of the second set item.

- the radiating element is defined by a first straight line passing through a central point of the radiating element and a second line perpendicular to the first straight line and passing through the central point, the excitation points being distributed only on the first and / or on the second straight line

- The radiating device comprises two slots extending longitudinally along the first straight line and the second straight line, the two slots ensuring the coupling of all the excitation points,

- at least one set from among the first set and the second set comprises at least a pair of the excitation points, the pair of excitation points comprising two excitation points coupled to the transmitting circuit and / or receiving so that a differential signal is intended to be circulated between the radiator and the transmission circuit,

- at least one set from among the first set and the second set comprises a first quadruple of the excitation points, the radiating element being defined by a first straight line passing through a center of the radiating element and a second line perpendicular to the first right and passing through the center points of excitation of each first quadruplet of points of excitation comprise a first pair of excitation dots composed of excitation points disposed substantially symmetrically with respect to said first straight line and a second pair of excitation points composed of excitation points disposed substantially symmetrically with respect to said second straight line,

- the excitation points of the first quadruplet points are located at a distance from the first straight line and the second straight line,

- each set comprises a first quadruple of excitation points along the first straight line and the second straight line,

- each set consists of a first quadruplet points, the excitation points of each first quadruplet points being situated on one side of a third straight line lying in the plane defined by the radiating element, through the central point and being a bisector of the angle formed by the first and the second straight line,

- the assembly comprises a second quadruple of excitation points away from the first straight line and the second line comprising: - a third pair made up of excitation points disposed substantially symmetrically with respect to said first straight line, the points of the third pair of points being arranged on the other side of the second straight line with respect to the first pair of excitation of said set point,

- a fourth pair consisting of excitation points disposed substantially symmetrically with respect to said second straight line, points of the fourth pair of points being arranged on the other side of the first right with respect to the second pair of points excitation of said assembly,

- each set from among the first set and the second set includes a first and a second quadruplet points,

- the antenna comprises phase shifting means for introducing a first phase difference between a first signal applied, or derived from, the first pair of excitation points and a second signal applied to, or from, respectively, the second pair of excitation points and a second phase shift of said set being different from the first phase difference between a third signal applied to, or derived from, respectively, the third pair or from the third pair of excitation points of said assembly and a fourth signal applied to, or derived from, respectively, the fourth pair of excitation of said set point,

- the first quadruplet points and the second quadruple of points of at least one assembly being excited by different frequencies or signals being summed separately.

Advantageously, generally applicable in particular to the two embodiments, each amplification channel of the first type is associated with an amplification chain of the second type, these amplification channels being coupled to the excitation points arranged for transmitting or receiving respective elementary waves linearly polarized in the same direction. In other words, this direction is common to the amplification channels connected to one another.

The invention also relates to an antenna comprising a plurality of elementary antennas according to any one of claims

preceding, wherein the radiating elements form an array of radiating elements.

Advantageously, the antenna comprises pointing phase shifting means used to introduce the first overall phase shifts between the signals applied to, or derived from, first quadruplets points of at least one set of points of the respective antenna elements and second overall phase shifts between the signals applied to the, or respectively from the, second quadruplets points of said set of points of the respective antenna elements, the first and second overall phase shifts may be different.

Other features and advantages of the invention will become apparent from reading the following detailed description, given by way of example and with reference to the accompanying drawings in which:

- Figure 1 shows schematically a first example of an antenna element according to a first embodiment of the invention,

- Figure 2 shows an antenna element in a side view,

- Figures 3, 4 and 5 show schematically three variations of the antenna element according to the first embodiment of the invention,

- Figure 6 shows a table of different polarizations can be obtained by the system of Figure 5,

FIGS 7, 8, 10 to 1 1 represent four variants of the elementary antenna of the invention Figure 4 schematically illustrates a antenna element according to a second embodiment of the invention,

- Figure 9 shows a table of different polarizations can be obtained by means of the antenna of Figure 8,

- Figure 12 shows an example of planar radiating device according to the invention,

- Figures 13 to 20 show seven examples of antenna element according to a second embodiment of the invention,

- Figure 21 schematically shows the reflection coefficients of the first excitation point of the antenna of Figure 13.

From one figure to another, the same elements are identified by the same references.

In Figure 1, an example of an elemental antenna A 1 is shown according to the invention comprising a planar radiating device 10 and a processing circuit or transmission / reception module 20a.

The planar radiating device 10 comprises a radiating element 1 January substantially planar, extending substantially in the plane of the sheet. The planar radiating device is a planar antenna better known under the name patch antenna.

The invention also relates to an antenna comprising a plurality of elementary antennas according to the invention. The antenna may be of the grating type. The radiating elements 1 1 where the planar radiating devices 10 of the antenna elements form a network of radiating elements. Advantageously, the radiating elements are arranged so that their respective radiating members 1 1 are coplanar and have a same orientation relative to a fixed reference plane of the radiating elements. Alternatively, the radiating elements are arranged in a different form.

The antenna is preferably an active antenna.

The planar radiating device 10 form a stack as shown in Figure 2. It comprises a radiating element 1 1, substantially plane, disposed above a layer forming the ground plane 12, a gap is provided between the element radiating 1 1 and the ground plane 12. This interval includes for example an insulating layer 13 electrically for example made of a dielectric material. Preferably, the radiating element 1 1 is a plate made of conductive material. Alternatively, the radiating member 1 1 has a plurality of stacked metal plates. It conventionally has a square shape. Alternatively, the radiating element has another shape, for example a disc-shaped or other parallelogram such as a rectangle or a rhombus. Whatever the geometry of the

The antenna element comprises feed lines 51, 52, formed of conductors, that is to say runs, coupled with the radiating element 1 in one of the excitation respectively 1 or 2 points within the radiating element 1 January. This coupling allows the excitation of the radiating element 1 January.

The tracks are examples given frequency.

The coupling is for example realized by electromagnetic coupling slot. The planar radiating device 10 then comprises a feed plane 1 6 visible in Figure 2 carrying the ends of the supply lines. 6 is plane 1 are advantageously separated from the ground plane 12 by a layer of insulating material 17, for example a dielectric. The planar radiating device 10 also includes at least one slot f formed in the layer forming the ground plane. The ends of the supply lines 51, 52 are disposed so as to overlap the corresponding slot by f below, the radiating member 1 1 is located above the layer forming the ground plane 12. The points excitation 1 and 2 are then situated to the right of the slot f and the end of the supply line 51, 52 correspondingly. The feed lines are connected to terminals of the corresponding channels. In Figure 1, the projection of the slot f is shown in dashed lines. In the embodiment of Figure 1, a slot f provided for both excitation points. Alternatively, there is provided a slot excitation point by or for a plurality of excitation points, for example a pair of points of excitation to be excited differentially or more pairs. For clarity, the slots are not shown in all figures. The slots are not necessarily rectangular, other shapes can be considered. the projection of the slot f is shown in dashed lines. In the embodiment of Figure 1, a slot f provided for both excitation points. Alternatively, there is provided a slot excitation point by or for a plurality of excitation points, for example a pair of points of excitation to be excited differentially or more pairs. For clarity, the slots are not shown in all figures. The slots are not necessarily rectangular, other shapes can be considered. the projection of the slot f is shown in dashed lines. In the embodiment of Figure 1, a slot f provided for both excitation points. Alternatively, there is provided a slot excitation point by or for a plurality of excitation points, for example a pair of points of excitation to be excited differentially or more pairs. For clarity, the slots are not shown in all figures. The slots are not necessarily rectangular, other shapes can be considered. excitation to be excited differentially or more pairs. For clarity, the slots are not shown in all figures. The slots are not necessarily rectangular, other shapes can be considered. excitation to be excited differentially or more pairs. For clarity, the slots are not shown in all figures. The slots are not necessarily rectangular, other shapes can be considered.

Alternatively, the coupling is achieved by electrically connecting the end of the supply line to an excitation point of the radiating element. For example, at the end of the supply line, the driving current flows to the radiating element through the insulating material, for example by means of a metallized via for connecting the end of the line supply to a pin on the back of the radiating element at the point of the right to excite. The coupling can be effected on the same plane of the planar radiating element or "patch" by attacking by a printed microstrip line or "microstrip", connected to the edge of the radiating element. The excitation point is then located at the end of the supply line. The

The coupling may be performed in the same way or differently for the various excitation points.

What has been said applies to all of the invention embodiments.

According to the invention, the radiating element 1 1 comprises a first set of at least one excitation point of the compound excitation point 1 of Figure 1, and a second set of at least one excitation point , compound of point 2 in Figure 1. excitation points of the two sets are distinct. In other words, the two sets do not have in common.

The points of the two sets are coupled to signal amplification channels which are of two distinct types so that they have different amplification properties. This coupling is simultaneous. In other words, these amplification channels are configured to perform various signal processing. They then have different optimal impedances to the radiating device or they have different requirements in terms of impedance matching with the radiating device. One can for example be at least one configured transmission amplification system for amplifying a signal so as to deliver an excitation signal then applied to the radiating device for one of the sets of points and at least one chain reception amplification configured for receiving and amplifying a reception signal from a reception signal from the other set of points. two receiving amplifying channels may alternatively be provided having different powers and therefore different requirements in terms of impedance matching.

The invention adjusts the impedance of the excitation points of the two sets of points independently. Dedicating different excitation points to separate functions, for example the transmission and reception or transmission of high power signals and the emission of low-power signals, one can adapt the impedances seen by the different channels independently amplification. On the particular embodiment of Figure 1, the transmit and receive circuit 20a comprises a transmit amplifier chain 1 10a coupled to point 1 for amplifying signals from a circuit for generating non-microwave signals shown and outputting signals to energize the point 1 and a chain reception amplification 120a coupled to the step 2 to process signals from point 2. The two amplifier have different amplification properties. In other words, these chains have the amplifiers having different properties. The transmission 1 10a amplification chain is for example a power amplifier system in the field of electronic warfare, comprising a transmission amplifier configured to transmit signals, for example a power amplifier HPA 1 14a ( with reference to the English expression "High Power amplifier") and the reception amplifier chain comprises a measuring amplifier 1 16a configured to process signals from a sensor, here the radiating device 10, which is for example a low noise amplifier LNA (with reference to the English expression "Low Noise Amplifier"). The coupling between each transmit amplifier chain or reception and an excitation point 1 or 2 is done by means of a feed line 51 or respectively 52. ​​This is true in all the figures but the lines power associated with the excitation points are not referenced throughout the figures for clarity.

Each amplification channel is designed to have optimal performance when it is loaded (the output to a transmission amplifying chain or input for receiving amplifier chain) by a well-defined optimal impedance; it degraded performance when charged by a different impedance of this optimum value.

The optimum impedance of input or output of an amplification chain is substantially the optimum input impedance of the amplifier input or respectively the optimal output impedance of the channel's output amplifier amplification.

Advantageously, the excitation 1 and 2 points are positioned and coupled to the respective amplifier systems 1 10a or 120a such that each amplification chain 1 10a or 120a is charged substantially by its optimal impedance. It is said that there impedance matching.

Advantageously, the impedance loaded onto an amplification chain 1 10a or 120a is the impedance of the chain formed by the radiating device 10 coupled to the amplification system 1 10a or 120a, the excitation point 1 or 2, and each power supply line 51 or 52 coupling the radiating device 10 to the amplification system 1 10a or 120a to the corresponding excitation point. This string is a source when

coupled to a reception amplifying chain and a load when it is coupled to a transmit amplifier chain.

Therefore, the proposed solution optimizes consumption in transmit mode, and improve the noise factor, the receive mode. Therefore, it is possible to avoid having to make a compromise at the impedance matching can be costly performance or avoid to provide an impedance transformer.

The advantage of such a solution is the optimized impedance matching for both transmission and reception functions. It should be noted that the transmission signals are much stronger than the received signals and that the amplifiers of the transmission amplification chains including power amplification channels 1 10a have low output impedances optimal , typically of the order of 20 Ohms, and the amplifiers of the reception amplification chains including low noise amplification channels 120a have a higher impedance to optimal output, typically of the order of 100 Ohms, for which they have better noise figure.

Therefore, the points are advantageously positioned and coupled to channels of the transmit amplifier chain way of amplification 1 10a is loaded on an impedance having a resistive portion less than the impedance loaded onto the reception amplification chain 120a.

Impedance matching is preferably carried out by adjusting the positions of the excitation points.

On the particular embodiment of Figure 1, the distance between each excitation point and the center C is adjusted to adjust the impedance. The distance between each excitation point 1 and 2 from the center C varies in the same direction as its impedance. Point 1 closer to the center C than the point 2 has a lower impedance than the impedance of point 2.

More generally, in all variants of the first embodiment, the excitation points of the first and second sets have distinct impedances. These impedances are measured with respect to ground. On the embodiments of FIGS, the first set of excitation points have resistive portions of the impedances more

lower than the impedances of the parts of the second set. These impedances are measured with respect to ground.

When these two sets have different impedances, the excitation point which consist advantageously have identical impedances.

In an advantageous embodiment, the impedances of the feeders are negligible so that the impedance loaded onto an amplification chain 1 10a or 120a is substantially that of the radiating device 10 to the excitation point or between the points excitation coupled (s) to the amplification chain.

Advantageously, in order to achieve an optimal impedance matching, the transmitting the amplification chain output impedance 1 10a coupled to the excitation point, point 1 in Figure 1 is substantially the conjugate of the impedance of the radiating device 10 presented to said transmit amplifier chain 10a at said point 1 1 and the input impedance of the receiver amplifier chain 120a coupled to the point 2 is substantially the conjugate of the impedance of the radiating device 10 shown in 120a receiving amplifier chain to the point 2 in Figure 1. The input impedance or output of an amplification chain is substantially the input of the amplifier input impedance or respectively the output impedance of the

The proposed solution also achieves isolation of the reception amplification channel 120a relative to the transmitted wave when transmitting. Indeed, the 120 does reception amplification chain receives the signal emitted by the point 1, a portion equal to a ratio of the point 1 of the impedance module on the impedance module of point 2. If point 1 has an impedance of 20 Ohm corresponding to the optimal emission of the amplification chain output impedance 10a 1 and point 2 has an impedance of 100 ohms corresponding to the optimum impedance of the string input 120a receiving amplification, there is a 7 dB isolation between the two channels 1 10a and 120a. There ' is then not necessary to provide switch for switching between transmission and reception modes or to provide a circulator in order to avoid saturating, see destroy, the receiving amplifier system 120a during transmission. in strength is gained, reliability and detection accuracy (it should be noted that the influence switches on the noise factor at the reception, must be resistant to the total power and must be able to switch to the transmission mode switching frequency in receive mode ). It also gaining weight and cost compared to solutions comprising circulators. The integration of a circulator in the X-band mesh is very difficult because of the clutter. The solution also allows for the transmission and reception simultaneously. In Figure 1, the chain emission amplification 1 10a comprises a single one amplifier 14a, for example a power amplifier. Alternatively, it may include several amplifiers. The receiving 1 10a amplification system comprises an amplifier, for example low noise 1 16a. Alternatively, it comprises several. The 120a receiving amplifier chain further comprises means of protection such as a limiter 17a 1, for example a PIN diode, to protect the reception amplification chain 1 10a from external aggressions. These characteristics apply to all of the invention embodiments. Generally according to the first embodiment of the invention, the transmitting circuit and receiving antenna comprises a circuit own transmission providing signals for energizing the radiating element coupled to the first set of excitation points and a clean reception circuit to process receiving signals coming from the radiating element and coupled to the second set of points. Advantageously, the transmitting circuit is coupled to the first set of points and the receiving circuit is coupled to the second set of points. The transmission and reception circuit circuit are not coupled to common. In other words, each transmit amplifier chain is coupled to one or two points of the first set of points and each receiving amplifying channel is coupled to one or two points of the second set. The chains

In the example of Figure 1, each assembly includes an excitation point 1 or 2. In a variant of an antenna 1 is shown in Figure 3, at least one of the sets of radiating device 10a includes a pair of points excitation configured to be excited differentially. Duplication of the excitation points can increase the power of 3 dB in transmission with respect to the embodiment of Figure 1, when the pair of points is connected to a transmitting amplifier chain, and linearity of 3 dB reception with respect to the embodiment of Figure 1, when the pair of points is connected to a receiving amplifier chain. For the same received power, each receiver will receive only half the power.

Alternatively, the antenna comprises at least one pair of excitation points. Per pair of excitation dots, is meant in the following text, two excitation points which are positioned and coupled to the processing circuit so that the processing circuit is configured to excite the points of the pair by means differential signal, that is to say balanced, or for treating differential signals, or balanced, from the pair of points. The points of a same pair are thus at each instant, excited by opposite signals. excitation points of a pair of excitation points are coupled to a same chain of amplification and are the only points of excitation to be coupled to this amplifier chain.

In Figure 3, the first set of the excitation points is composed of a first pair of points of excitations 5+ and 5- and the second set of points of excitation is composed of a first pair of points 6+ and 6- excitation. In Figure 3, these points are located on the same straight line D1 of the radiating element 1 1 a of the radiating device 10a passing through the center C of the radiating element 1 1 a. They are arranged substantially symmetrically relative to the center C so as to have the same impedance.

The processing circuit 20 or transmission / reception module includes a transmission amplification system 1 10 and a receiving amplifier chain 120. 5- 5+ points are positioned and coupled to the amplification chain of transmission 1 10 so that the transmit amplifier chain excites the 5+ and 5- point by means of a differential signal. The transmission amplification system 1 10 includes a transmission amplifier 1 14, for example a power amplifier. The transmission amplification system 1 10 is coupled to the point 5+ and 5- via respective power supply lines 51 a and 51 b. On the nonlimiting example of Figure 3, channel 1 10 is configured to amplify or two opposite-phase signals 180 ° injected received at its input.

The receiving amplifier chain 120 is for example a low noise amplifier chain 120 comprising a measuring amplifier 1 14, for example a low noise amplifier. It differs from that of Figure 1 in that it is proper to acquire differential signals. This channel 120 is coupled to 6+ and 6- point so as to acquire the differential signals from these points. The channel 120 allows to amplify and outputting a differential signal. Alternatively, it may issue an asymmetric signal as in Figure 1. The chain 120 is coupled to the points respectively 6+ 6 via respective power supply lines 52a and 52b. The receiving amplifier chain 120 also includes a means of protection such as a limitation 1 17 protect the chain

Advantageously, the excitation point 5+, 5-, +, 6 are positioned and coupled to the respective amplification Channels 1 10 or 120 so that each amplification system 1 10 or 120 is loaded substantially by its optimal impedance . Advantageously, the impedance loaded onto an amplification system 1 10 or 120 is the impedance of the chain formed by the radiating device 10 coupled to the amplification system 1 10 or 120 between the 5+ excitation points, 5 - or 6+, 6- and by the lines 51a and 51b or 52a or 52b coupling the radiating device 10, that is to say the point 5+, 5- and 6+, 6, the chain corresponding gain 1 10 or 120.

Thus, points of the two sets exhibit different impedances as specified above.

Advantageously, but not necessarily the impedance loaded onto each amplification system 1 10 or 120 is substantially the impedance of the radiating device 10a measured between the two excitation points 5+ and 6+ and 5-or 6- coupled corresponding amplification system 1 10 or 120.

Advantageously, as in the previous figure, the impedance of the radiating device 10 presented to the transmit amplifier chain between the point 5+ and 5-, that is to say, the differential impedance of the radiating device 10a between these points is substantially the conjugate of the output impedance of the receiving amplifier system 1 10 and the impedance of the radiating device 10a shown to the receiving amplifier chain between 6+ and 6- point is substantially equal to the input reception amplifying channel impedance 120. These impedances are real.

In Figure 4, an antenna 1b is shown which is a variant of Figure 3. This variation differs from that of Figure 3 in that one of the sets, here the first set is composed of a pair 5+ excitation points, 5- excited differentially as shown in Figure 3 and the other set of points, by the second set is composed of an excitation point which is the point 2 excited asymmetrically as in Figure 1.

In Figures 1, 3 and 4, the excitation points of the first and second set are arranged on a same straight line D1 of the radiating element through the center C of the radiating element. This allows for the excitation of all the points by means of a single slot f represented in Figure 1 extending along the straight line D1, and so a certain ease of manufacture. In the embodiment of the figures, the straight line D1 is parallel to one side of the radiating element 1 January. Alternatively, all the excitation points are arranged on a straight line passing through the center of the radiating member 1 1 and two peaks of the radiating element 1 January. Alternatively, at least one of the sets of points of the two respective sets are arranged in or close to orthogonal two respective sides of the radiating element 1 January. Alternatively, the points of two respective sets are arranged on two orthogonal lines passing through the center C as shown in Figures 1 1 to 1 2, which will be described later. The coupling of all points can be realized by means of only two slits extending along the respective straight lines.

In a variant shown in Figure 5, each assembly comprises two quadruplets of excitation points 1 a + 1 a-, 2a +, 2a and 3a +, 3a, 4a +, 4a- and respectively 1 b + 1 b, 2b + , 2b- and 3b +, 3b-, 4b +, 4b-. Each quadruplet of points comprises two pairs of the excitation points arranged in respective orthogonal straight lines, the excitation points of each pair of excitation points are arranged so as to be excited differentially.

In the specific example of Figure 5, the plane of the radiating element 1 1 c 10c planar radiating device is defined by two orthogonal directions. These two directions are the right first D1 and second D2 right. Each of these orthogonal directions passes through the center C. As non-limiting embodiment of Figures 5 to 10, these lines are parallel to respective sides of the radiating element is rectangular. This rectangle is a square, in the nonlimiting example of these figures.

The first set of excitation points comprises a first quadruple of excitation points are all located remotely of the lines D1 and D2, that is to say which are excluded from these straight lines D1 and D2, said first quadruplet points comprising:

- a first pair of excitation points 1 a +, a- 1 composed of an excitation point a + 1 and an excitation point 1 a- arranged substantially symmetrically to each other relative to the right first D1, - a second pair of excitation points + 2a, 2a consists of an excitation point a and 2a + 2a excitation point disposed substantially symmetrical manner from each other with respect to the right second D2.

The first set of excitation points comprises a second quadruple of excitation points are all located remotely of the lines D1 and D2, the second quadlet of points comprising:

- a third pair of the excitation points + 3a, 3a consisting of an excitation point 3a + and 3a- excitation point arranged substantially symmetrically with respect to the first straight line D1, the excitation point 3a + and 3a of the third pair of points being arranged on the other side of the second straight line D2 relative to the first pair of excitation points 1 a +, a- 1,

- a fourth pair of excitation points 4 +, 4a- comprising an excitation point + 4a and 4a excitation point arranged substantially symmetrically with respect to the second straight line D2, the excitation points 4 and 4a + the fourth pair of points being arranged on the other side of the first straight line D1 relative to the second pair of points of excitation + 2a, 2a.

The points of each pair are substantially symmetrical to one another by orthogonal symmetry axis D1 or D2.

excitation points of the two quadruples of points are distinct. In other words, two quadruplets of points present no common excitation points. The various pairs do not have in common excitation points.

The second assembly includes a first quadruplet of points comprising a first pair 1b +, 1 b and a second pair 2b + 2b-presenting the same characteristics as the first quadruplet point 1 a + 1 a-, 2a + 2a- points of first set listed above but different impedances impedances of the first quadruplet points. The second assembly further includes a second quadruplet of points comprising a third pair 3b +, 3b- and a fourth pair 4b +, 4b-presenting the same characteristics as the second quadruplet points 3a +, 3a, 4a +, 4a of the first set listed -Dessus but different impedances.

Advantageously, the points of a pair of excitation points are arranged so as to have identical impedances measured with respect to ground so as to be excited differentially. Advantageously, all points of the same set have the same impedance. To this end, the embodiment of Figure 5 wherein the radiating element 1 1 is square and straight lines D1 and D2 parallel to respective sides of the square, the points of a same set of points are located substantially at the same distance the center C and a same distance between the points of each pair of this set. The first and third pair of each set are then symmetrical to each other relative to the straight line D2 and the second and fourth pair of each set are symmetrical to

The points of the first set have lower impedances than those of the second set. For this purpose, in the example of Figure 5, the points of each pair of points are separated by the same distance, and the points of the first set are closer to the center than the second set.

The module transmitting / receiving antenna 20c 1 c comprises a transmission circuit A comprising four transmit amplification chains 21 to 24 identical to 10 of Figure 3. Each chain amplification chain transmission 21, 22, 23 or 24 is coupled to a pair of excitation points 1 a + and a- 1, and 2a + 2a, 3a and 3a or 4a + + 4a respectively and the first set of excitation points is adapted to apply a differential excitation signal to the pair of excitation points. The module transmission / reception 20c comprises a receiving circuit B comprising four reception amplification chains from 31 to 34 identical to the low noise amplifier chain 120 of Figure 3. Each chain

The pair of points 1 a + and 1 a- coupled to the chain 21 is for emitting a polarized wavelet rectilinearly D2 direction as the pair of points 3a + 3a coupled to the chain 23 while the pairs 2a + 2a and 4a +, 4a- respectively coupled to channels 22 and 24 are for emitting respective elementary waves linearly polarized in the direction of the straight line D1.

The pairs of points 1 b + and 1 b coupled to the chain 31 is for detecting a polarized wavelet rectilinearly D2 direction as the pair of points 3b +, 3b- coupled to the chain 33, whereas the even 2b + 2b- + and 4b, 4b-coupled to the channels, respectively 32 and 34 are for detecting the elementary wave linearly polarized in the direction of the straight line D1.

Advantageously, the excitation points are positioned and coupled to the respective amplifier systems 21 to 24 and from 31 to 34 so that each amplification chain from 21 to 24 and 31 to 34 is loaded substantially by its optimal impedance. Advantageously, the impedance loaded onto an amplification channel 21, 22, 23, 24, 31, 32, 33, 34 is the impedance of the chain formed by the radiating device 10 coupled to the amplifier chain between the two excitation points a + 1 and 1 + a- or 2a and 2a-4b + and 4b- and supply lines connecting the radiating device 10c to the corresponding amplification channel.

Advantageously, but not necessarily the impedance loaded onto each amplification chain, e.g., 21, is substantially the impedance of the radiating device 10c measured between the two excitation points 1 a + and a- 1, coupled to the chain amplifier 21 and the corresponding amplification channel 21.

Advantageously, the impedance of the radiating device 10 shown in each transmit amplifier chain 21, 22, 23 and 24 respectively between the pairs of respective points of the first set 1 a + and a- 1, and 2a + 2a, 3a + and 3a and 4a respectively and + 4a- has a resistive portion less than the impedance of the radiating device 10 presented to each receiving amplifier chain 31, 32, 33 and 34 between each pair of items 1 and b + 1 b, 2b and + 2b-, 3b + and 3b- and 4b respectively and + 4b-.

Advantageously but not necessarily, the impedance of the radiating device 10 shown in each transmit amplifier chain 21, 22, 23 and 24 respectively between the pairs of respective points of the first set 1 a + and a- 1, 2a and 2a + , 3a + and 3a and 4a respectively and + 4a is substantially the conjugate of the output impedance of the transmitting amplifier chain 21, 22, 23 and corresponding the impedance of the radiating device 10 shown in each chain reception amplification 31, 32, 33 and 34 between each pair of point 1 b + and b- 1, 2b- 2b and +, + 3b and 4b respectively and 3b- + and 4b- is substantially the conjugate of the input impedance chain amplification of reception 31, 32, 33 and 34 respectively, corresponding.

For clarity, is not shown, in Figure 5, complete contact between the respective amplification chains and the planar radiating means. In contrast, it was indicated how excitation point is coupled to each input of each transmit amplifier chain 21 to 24 and each output of each receiving amplifier chain 31 to 34.

During transmission, an excitation signal SE applied by generation electronics an input microwave signal of the transmitting / receiving module 20c is divided into four differential excitation signals applied at the input of power amplifier chains 21 to 24. the respective four differential excitation signals are identical to the respective phases and amplitudes near optionally.

The transmitting circuit A includes a splitter 122 for dividing the excitation signal SE in common two excitation signals, can be asymmetrical as in Figure 1 or symmetric (that is to say, differential or balanced) respectively injected at the input of phase shifters to respective transmission 25, 26. Each phase shifter 25, 26 outputs a differential signal (as in Figure 5) or an unbalanced signal. The signal leaving the first phase shifter transmission 25 is divided and injected at the input channels 21 and 23. The output signal from the second phase shifter transmission 26 is divided and injected at the input channels 22 and 24.

The respective emission amplification chains 21 to 24 are advantageously coupled to respective excitation points so that the elementary waves generated by the pair 1 a +, a- 1, and the pair 3a +, 3A are polarized in the same direction and so that the elementary waves excited by the pair + 2a, 2a and the pair + 4a and 4a are polarized in the same direction. Thus, the electric fields of the excitation signals applied to pairs 1a + 1 + a- and 3a, 3a have the same meaning. Thus, the two pairs of points a + 1, 1 + a- and 3a, 3e can deliver the same signal only from two points of excited asymmetrically. The power to be supplied by each amplifier chain 21 and 23 is divided by two and the current to be supplied by this chain gain 1 1 is then divided by square root of two. The ohmic losses are lower and power amplifiers easier to achieve (less powerful). Likewise, the electric fields of the excitation signals applied to pairs 2a +, + 2a and 4a, 4a have the same meaning.

The transmitting circuit A comprises phase shifting means in transmission 25, 26 comprising at least one phase shifter for introducing a first phase, said first phase shift in emission between the signal applied to the first pair 1 a +, a- 1 and the signal applied to the second pair 2a + 2a and introduce the same first transmission phase shift between the signal applied to the pair + 3a, 3a and the signal applied to the pair + 4a, 4a. Elementary excitation signal injected at the input channels 21 and 23 are in phase. Elementary excitation signal injected at the input channels 21 and 24 are in phase.

Advantageously, the first phase shift transmission is adjustable. The array antenna preferably comprises an adjusting device 35 for adjusting the first phase shift in emission so as to introduce a first phase shift by predetermined transmission.

Each pair of points of excitation generates a wavelet.

With the first phase shift transmission, the elementary waves emitted by the pairs a + 1, 1 + a- and 3a, 3a are phase shifted with respect to the elementary waves emitted by the pairs 2a +, + 2a and 4a, 4a. Recombinantly in air elementary wave, we obtain a total wave which it is possible to vary the polarization by varying the first phase shift transmission. Examples of relative phases between the transmission signals injected on the conductors coupled to the respective coupling points are given in the table of Figure 6 and the resulting polarizations. The vertical polarization is polarization along the z axis shown in FIG 5. Two points excited in phase opposition, separated by 180 °, have voltages of opposite instantaneous excitation. For exemple, the first row of the table of Figure 6 illustrates the case where the conductors coupled to points 1 + 2a + 3a + 4a + are brought to the same voltage and the conductors coupled in points 1 a-, 2a, 3a, 4a - are brought to the same voltage, opposite to the previous one. The voltage differential is then symmetrical relative to the straight line D3. The polarization is oriented along this straight, vertically oriented. Linear polarization at + 45 ° is obtained by exciting only the pair 1 a +, a- and 1 pair + 3a, 3a with differential excitation signals in phase without exciting pairs 2a +, + 2a and 4a, 4a. This is achieved for example by adjusting the gain of the amplifiers 14 January in issuing zero power. To this end, the amplifiers have a variable gain and means for adjusting the gain not shown. In the example of the fifth line, the phase shifts between the points remain the same over time. The evolution of the phases over time produces a right circular polarization.

In reception, reception received by the pairs of respective excitation points of the signals 1 and b + 1 b, 2b and 2b- + 3b + and 3b-, 4b and 4b-+ are respectively applied to the input of the amplification chains transmission 31, 32, 33, 34 respective. Each receiving amplifier chain supplies a differential signal. Alternatively, reception amplifying chain includes a combiner so as to deliver an asymmetric signal.

elementary outgoing receiving the signals of the channels 31 and 33 are injected to the input of a first reception phase shifter 29 and chains 32 and 34 are injected to the input of a second receiving phase shifter 30. The phase shifters 29, 30 are used to introducing a first phase difference in reception between the reception signals delivered by the channels 31 and 33 and those delivered by the channels 32 and 34. the outgoing reception signals of the reception phase shifter 29, 30 are summed by an adder 220, module 20, until the reception signal resulting SS is transmitted to the electronic offset acquisition.

Thus, the receiving circuit B comprises phase shifting means receiving 29, 30 make it possible to introduce a first phase shift between reception of reception signals from the pairs b 1 + b 1 + and 2b, 2b- and between signal receiving from pairs 3b +, 3b- and 4b +, 4b-. On the non-limiting embodiment of Figure 1, these means are situated at the outlet channels 31-34.

Advantageously, the first phase shift in reception is adjustable. The device advantageously comprises an adjustment device for adjusting the phase shift which is the reception device 35 of the non-limiting embodiment of Figure 5.

The relative phase introduced by the phase shifting means in transmission 25, 26 can be same as those introduced by the phase shifting means in receiving device 29, 30. This will receive the elementary waves having the same phases as the elementary waves and so make measurements over a total reception wave having the same polarization as the total wave emitted by the antenna element. Alternatively, these phases may be different.

Advantageously, these phases can be advantageously independently adjustable. This allows to transmit and receive signals having different polarizations.

Alternatively, the number of phase shifters is different and / or phase shifters are arranged otherwise whether in input power amplification chains or at the output of low noise amplification channels.

Advantageously, the antenna comprises said score phase shifting means for introducing adjustable overall phase shifts between the excitation signals applied to the points of the respective antenna elements of the antenna and / or between the reception signals from points the respective antenna elements of the antenna.

In the nonlimiting example of Figure 5, these means comprise a control device 36 generating a control signal to adjusting means 35. The controller 36 generates a control signal SC comprising specific commander phase shifts of signals the introduction of the first phase shifts in transmission and reception on the signals input to each phase shifter transmitting and respectively receiving and global signals controlling the introduction of the global phase shift on the signals input from each transmit phase shifter and receiving, respectively. The controller 36 sends these control signals to the adjusting device 35 so that it controls the phase shifter for these phase shifts they introduce on the signals they receive.

issued by the elementary antennas of the array, to select the pointing direction of the wave emitted by the antenna and the wave received by the antenna. The electronic scanning of an array antenna based on the phase shifts applied to the antenna elements constituting the network, the scanning being determined by a phase law.

The antenna according to the invention has many advantages.

Each transmit amplifier chain 21 to 24 is clean, in transmission, applying a differential signal and each transmit amplifier chain 31 to 34 is unique in reception to acquire a differential signal. Each string already operating in the differential signal avoids having to interpose a component such as a balun (for "balanced unbalanced transform") to switch between a differential signal to an unbalanced signal. However, such intermediate component degrades the power efficiency. The power efficiency of the device is improved.

To operate with high power, the invention uses transmission amplification channels 21 to 24 coupled to four quadrature bias port pairs and four reception amplifying channels 31 to 34 coupled to four bias port quadrature pairs, each channel operating at a nominal power compatible with the maximum acceptable power through technology implementation to make it.

The power of the electromagnetic waves emitted or received by the radiating means may be higher than the nominal operating power of the chain coupled to this pair of excitation points. Each pair of exciting points of the radiating element excited differentially generates a wavelet. The antenna works double differential transmission and reception. The power of the elementary wave transmitted by each pair of points is two times greater than the nominal transmit power of the transmitting amplifier chain 21-24.

This is particularly advantageous when the rated power is close to the maximum power allowed by the implementation technology for achieving emission amplification channels 21 to 24. Although at the level of each driver circuit, power remains below maximum power, the elementary antenna allows to transmit waves to a higher power.

The choice of technology fixed plane radiating device the voltage to be applied to the excitation points. The higher the voltage, the higher the current is low in power and equal impedance and ohmic losses are low. For an identical impedance, dividing the power output by two results in a division of power per square root of two. The proposed solution by adding the power directly to the patch or radiating element 1 1 c, ohmic losses are therefore greatly diminished.

As stated previously, power summation is carried out directly at the excitation points. It is not necessary to emit four times more power, to provide emission amplification chains having four times more powerful amplifiers. It is not necessary to summon outside of the radiating means of the signals from limited power amplifiers, for example by means of adders ring or Wilkinson. The invention limits the number of drivers used and the ohmic losses in conductors and therefore the power generation to compensate for these losses. It is not necessary to limit losses to the summations of energy in the MMIC. If the summations are made in MMICs, losses are dissipated in this already critical location. The heating of the antenna and the ohmic losses are thus reduced.

Furthermore, by exciting the excitation points of each pair of differentially, each pair of points emits an elementary wave linear polarization. By applying a phase shift between the excitation signal of the first pair of points 1 a +, a- 1, and the third pair of 3a- points 3a + and the excitation signals of the second pair of points + 2a, 2a and the fourth pair of points + 4a, 4a orthogonal to the first and third pair of point 1 a +, a- and 3a- 1, 3a +, the radiating element 1 1 c is adapted to generate by itself a polarized wave by recombination in the space of four elementary waves.

This avoids the use of interposed polarization selecting switches between the transmitting / receiving module 20c and the radiating element to change a direction in which the radiating element is to be energized. This also allows to directly connect this unit 20c to the excitation point and thus to increase the power output,

that is to say to limit losses. The heating of the elementary antenna is reduced.

Furthermore, the recombination in the space of four elementary waves emitted by the radiating element results in a total wave whose power is four times greater than the power of each wavelet.

In reception, the total incident wave is split into four elementary waves transmitted to the low noise amplifying respective channels 31 to 34 and is reconstituted by summation. A wavelet has a capacity four times lower than the total incident wave. This allows the antenna to be more robust with respect to external aggressions, such as illumination of the antenna by a device performing an intentional or unintentional interference. The risk of damage to low noise amplifiers 1 1 6 are limited. For example, assaults strong fields will be reduced by the fact that the elementary signals are not received in the optimal polarization but at 45 ° (when emissions are either horizontal or vertical polarization, but not diagonally). The

All benefits can be achieved through the judicious arrangement of excitation points on the radiating plane.

In Figure 7, another alternative antenna element 1 is shown according to the first embodiment of the invention.

The planar radiating device 10c is identical to that of Figure 5. The antenna comprises an Ad transmitting circuit comprising the same emission amplification channels 21-24 as in Figure 5 and a Bd receiving circuit comprising same reception amplifying channels 31 to 34. These channels are coupled in the same manner as in Figure 5 to the respective pairs of excitation points.

In contrast, the transmitting / receiving unit 20d differs from that of Figure 5 by the phase shift means. It comprises emission phase shifting means comprising at least one phase shifter for introducing a first phase shift in emission between the excitation signals applied to the pairs of excitation points a + 1, 1 + a- and 2a, 2a and a second phase shift in emission between the excitation signals applied to the pairs of points 3a +, + 3a and 4a, 4a, both in transmission phase shifts may be different. This allows emit waves with different polarizations by means of two quadruplets of points.

In the nonlimiting example shown in FIG 7, these show in phase shift means comprises a first phase shifter 125a and transmitting a second phase shifter 125b to transmit a receiving signal even possibly at an amplitude near, and each introducing a phase shift on the received signal so as to introduce the first phase shift in emission between the excitation signals applied to the pair 1 a +, a- and 1 pair + 2a, 2a. The phase shift means comprises a third 126a and fourth 126b transmit phase shifter receiving the same signal, possibly at an amplitude near, and each applying a phase shift to the signal so as to introduce the second phase difference between the applied excitation signals on the pair + 3a, 3a and 4a on the pair +, 4a. The first and second emission phase may be different. The excitation signals from the phase shifters 125a and 125b are injected into respective channels 21 and 22. The excitation signals from the phase shifters 126a and 126b are injected respectively input channels 23 and 24. It is thus possible simultaneously emit two beams having different polarisations using the two quadruplets of points.

The receiving circuit Bd comprises phase shift means receiving 129a, 129b, 130a, 130b for introducing a first phase difference in reception between the excitation signals applied to the pairs of the excitation points 1 b +, b- 1 and 2b +, 2b- and a second phase difference in reception between the excitation signals applied to the pairs of points 3b +, 3b- and 4b +, 4b- these two phase shifts may be different. Post reception signals to respective reception amplification channels 31-34 are injected into respective receiving phase shifters 129a, 129b, 130a, 130b each capable of introducing a phase shift on the signal it receives. Each reception signal is injected into one of the phase shifters.

Advantageously, the phase shifts introduced between the excitation signals and / or receiving point pairs 1a + 1 a- and 2a +, 2a and / or 1b +, 1 b and 2b +, 2b- and between pairs 3a + , 3a and 4a + 3b and 4a + 4b + and 3b-, 4b- are identical. Alternatively, these phase shifts may be different. This allows to transmit and / or receive two waves whose polarization may be different.

Advantageously, the phase shifts are adjustable.

Advantageously, the phase shifts introduced between the transmission signals and / or reception applied to the pairs of points a + 1, 1 + a- and 2a, 2a and / or from the pairs b 1 + b 1 + and 2b, 2b- and between the signals applied to pairs 3a +, + 3a and 4a, 4a and / or from pairs 3b +, 3b- and 4B +, 4b- may advantageously be independently controlled. It is then possible to independently adjust the polarizations of elementary waves emitted by the first quadruplet points 1 a + 1 a-, 2a + 2A and the second quadruplet points 3a +, 3a, 4a +, 4a of the first set or measured by the first quadruplet points b + 1, 1 b, 2 b + 2b- and the second quadruplet points 3b +, 3b-, 4b +, 4b- the second set.

The array antenna preferably comprises an adjusting device 35 for adjusting the phase shifts in transmission and in reception.

2b- second sets of respective antenna elements and second overall phase shifts in reception between the receiving signals from the second quadruplets points 3b +, 3b-, 4b +, 4b- second sets respective elementary antennas of the array, the first and second overall phase shifts in reception to be different. It is then possible to simultaneously emit two beams in two different directions and receive the two beams in two different directions.

Advantageously, the overall phase shifts in emission of the two sets of points are adjustable.

Advantageously, the overall phase shifts in transmission and / or reception are adjustable independently. pointing directions are adjustable independently.

In the nonlimiting example of FIG 7, the pointing phase shift means comprises the control device 36 generates a control signal SC comprising various signals controlling the introduction of the aforementioned phase shifts (global and non-global) to be applied to the signals received at the input of the various phase shifters and transmits these signals to the adjusting device 35 so that it controls the phase shifter for these phase shifts they introduce on the signals they receive.

The Figure 7 device also offers the possibility of measuring a beam in one direction and emit a beam in another direction simultaneously or to make two measurements in both directions simultaneously. It is possible to transmit and receive a signal in one direction and transmitting a transmit and receive communication in another direction. It is possible to make programs / cross receptions. It is possible to form a receive radiation pattern in transmission or covering the side lobes and diffuse lobes to allow secondary lobes opposition functions (OLS) for protecting the radar of intentional or unintentional interference signals. It is possible to transmit at different frequencies,

In the embodiment of Figure 7, the channel coupled to two quadruplets 1 a +, a- 1, 2a + 3a + and 2a, 3a, 4a +, 4a- are fed by means of two different power sources SOI S02. This allows to transmit two waves having different frequencies, one by the first quadruplet points 1 a +, a- 1, 2a + 2a and the other by the second quadruplet points + 3a, 3a, 4a + , 4a, when the sources deliver E1 and E2 drive signals of different frequencies. The antenna of Figure 7 can thus simultaneously transmitting two beams directed along two adjustable pointing directions independently at different frequencies. This possibility of two beams pointing in two directions simultaneously allows a dual beam equivalent: rapid scanning beam and a slow scan beam. For example a slow beam at 10 revolutions per minute, can be used in monitoring and rapid beam mode, at 1 revolution per second, can be used in tracking mode. This scanning mode is not interlaced as in the single beam antennas but can be simultaneous. The possibility of transmitting at different frequencies complicates the task of the radar detectors (ESM: Electronic Support Measures). This also allows a data link in one direction and a radar function in another direction. This embodiment also allows to emit two beams of different shapes. Can emit a narrow beam or a wide beam depending on the number of elementary antennas of the array are excited. can be used in monitoring and rapid beam mode, at 1 revolution per second, can be used in tracking mode. This scanning mode is not interlaced as in the single beam antennas but can be simultaneous. The possibility of transmitting at different frequencies complicates the task of the radar detectors (ESM: Electronic Support Measures). This also allows a data link in one direction and a radar function in another direction. This embodiment also allows to emit two beams of different shapes. Can emit a narrow beam or a wide beam depending on the number of elementary antennas of the array are excited. can be used in monitoring and rapid beam mode, at 1 revolution per second, can be used in tracking mode. This scanning mode is not interlaced as in the single beam antennas but can be simultaneous. The possibility of transmitting at different frequencies complicates the task of the radar detectors (ESM: Electronic Support Measures). This also allows a data link in one direction and a radar function in another direction. This embodiment also allows to emit two beams of different shapes. Can emit a narrow beam or a wide beam depending on the number of elementary antennas of the array are excited. is not interleaved as in the single beam antennas, but can be simultaneous. The possibility of transmitting at different frequencies complicates the task of the radar detectors (ESM: Electronic Support Measures). This also allows a data link in one direction and a radar function in another direction. This embodiment also allows to emit two beams of different shapes. Can emit a narrow beam or a wide beam depending on the number of elementary antennas of the array are excited. is not interleaved as in the single beam antennas, but can be simultaneous. The possibility of transmitting at different frequencies complicates the task of the radar detectors (ESM: Electronic Support Measures). This also allows a data link in one direction and a radar function in another direction. This embodiment also allows to emit two beams of different shapes. Can emit a narrow beam or a wide beam depending on the number of elementary antennas of the array are excited. This also allows a data link in one direction and a radar function in another direction. This embodiment also allows to emit two beams of different shapes. Can emit a narrow beam or a wide beam depending on the number of elementary antennas of the array are excited. This also allows a data link in one direction and a radar function in another direction. This embodiment also allows to emit two beams of different shapes. Can emit a narrow beam or a wide beam depending on the number of elementary antennas of the array are excited.

The module transmitting / receiving 20d includes a first distributor 21 1a for dividing the excitation signal E1 from the first source SO1 into two identical signals injected at the input of phase shifters 125a and 125b transmit. The circuit 120 comprises a second distributor 21 1b for dividing the excitation signal E2 from the second SO2 source into two identical signals injected at the input of the phase shifters 126a and 126b transmit.

On the nonlimiting example of FIG 7, the two signals from the first phase shifter 129a receiving input receiving reception signals from the first pair of excitation points b 1 + b 1 and the second receive phase shifter 129b receiving at its input receiving signals from the second pair of excitation points 2b +, 2b- are summed by a first adder 230a for generating a first output signal SS1. The two signals from the third phase shifter 130a receiving input receiving reception signals from the third pair 3b +, 3b- and fourth phase shifter 130b receiving input receiving the reception signals from the fourth pair of the excitation points 4b +, 4b- are summed by means of a second adder 230b to generate a second output signal SS2. The signals from the respective adders are separately transmitted to the electronic offset acquisition. This allows to differentiate between received signals having different frequencies. The signals from the two quadruplets of points 1 b + 1 b, 2b + 2b- and 3b +, 3b-, 4b +, 4b- of the second set being summed separately, it is possible to form a receiving antenna covering the side lobes and diffuse to allow opposition functions of secondary lobes (OLS) for protecting the radar of intentional or unintentional interference signals. This allows to differentiate between received signals having different frequencies. The signals from the two quadruplets of points 1 b + 1 b, 2b + 2b- and 3b +, 3b-, 4b +, 4b- of the second set being summed separately, it is possible to form a receiving antenna covering the side lobes and diffuse to allow opposition functions of secondary lobes (OLS) for protecting the radar of intentional or unintentional interference signals. This allows to differentiate between received signals having different frequencies. The signals from the two quadruplets of points 1 b + 1 b, 2b + 2b- and 3b +, 3b-, 4b +, 4b- of the second set being summed separately, it is possible to form a receiving antenna covering the side lobes and diffuse to allow opposition functions of secondary lobes (OLS) for protecting the radar of intentional or unintentional interference signals.

Alternatively, both E1 and E2 drive signals have the same frequency. One can thus obtain a more powerful total wave as in the embodiment of Figure 5 or emit two signals of the same frequency in two different directions and / or having different polarizations.

In Figure 8, an antenna element is shown one of which is another variant of the first embodiment of the invention.

The antenna element 1 of Figure 8 differs from Figure 5 in that the radiating element 1 1 e of the 10th radiating device includes a first set of points including only the first quadlet of points 1 a +, a- 1 , + 2a and 2a and in that it comprises a second set of points including only the first quadlet of points b + 1, 1 + b and 2b and 2b-. The transmission / reception associated 20e differs from that of Figure 5 in that it comprises only part of the transmitting / receiving device coupled to the excitation points. In Figure 8, as in Figures 10 to 1 1, the adjusting device 35 and the controller 36 have not been shown for clarity. The fact to excite the radiating element by two signals excitation applied to pairs of excitation points in quadrature to each other makes it possible to symmetrize the transmitting / receiving of elementary antenna pattern. This antenna element is adapted to emit a wave whose polarization is adjustable and receiving a wave according to an adjustable polarization direction. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. excitation located in quadrature with each other makes it possible to symmetrize the transmitting / receiving of elementary antenna pattern. This antenna element is adapted to emit a wave whose polarization is adjustable and receiving a wave according to an adjustable polarization direction. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. excitation located in quadrature with each other makes it possible to symmetrize the transmitting / receiving of elementary antenna pattern. This antenna element is adapted to emit a wave whose polarization is adjustable and receiving a wave according to an adjustable polarization direction. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. other allows to symmetrize the transmission pattern / reception antenna element. This antenna element is adapted to emit a wave whose polarization is adjustable and receiving a wave according to an adjustable polarization direction. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. other allows to symmetrize the transmission pattern / reception antenna element. This antenna element is adapted to emit a wave whose polarization is adjustable and receiving a wave according to an adjustable polarization direction. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. This antenna element is adapted to emit a wave whose polarization is adjustable and receiving a wave according to an adjustable polarization direction. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. This antenna element is adapted to emit a wave whose polarization is adjustable and receiving a wave according to an adjustable polarization direction. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8. Examples of phases of the injected signals on the conductors coupled to respective coupling points are given in the table of Figure 9 and the obtained polarizations. for example the first line title is considered. Points 1 and a + 2a + have the same excitation (same phases) and points 1 a- and 2a have the same excitation opposite to that of the other points. The polarization is vertical, that is to say along the z axis shown in Figure 8.

This antenna element also allows for array antennas for transmitting a total wave whose direction of

score is adjustable but with power two times lower than in Figure 5.

Advantageously, the excitation points 1 a +, a- 1, 2a + 2a, 1b + 1-b and 2b + and 2b- of the elementary antenna of Figure 8 are located on the same side of a third straight line D3 located in the plane defined by the radiating element and passing through the center point C and being a bisector of the angle formed between the lines D1 and D2. When the radiating element is square and the straight line D1 and D2 parallel to the respective sides of the square, the third straight line joining the two vertices of the square. This frees up a half of the radiating element to realize other types of excitation for example.

Advantageously, each first quadruplet points 1 a-, a + 1 and 2a + 1 and 2a-b, b + 1 and 2b +, 2b- of Figures 5 and 7 are also located on the same side of the straight line D3.

In Figure 10, an antenna element is shown 1f which is another variant of the first embodiment of the invention. The antenna element of Figure 10 differs from that of Figure 8 by arranging the points of the two sets quadruplets. More specifically, the antenna element of Figure 10 differs from Figure 8 in that the excitation points of the first set 1 a-, a + 1 and + 2a, 2a are located on the other side of the third right D3 with respect to the excitation points of the second set 1 b, 1 b and 2b + + 2b-. Therefore, the excitation points 1 a + and a- 1 are located on the other side of the straight line D2 in relation to items 1 b + and b- 1 and points 2a + and 2a are located on the other side of the straight line D1 with respect to the points + and 2b- 2b.

In Figure 1 1, there is shown an elementary antenna 1g which is another variant of the first embodiment. This antenna element differs from that of Figure 8 by the arrangement of points quadruplets of the two sets on the radiating member 1 1 g of the radiating plane 10g device. The arrangement of the points 1 a + 1 a- and 1 b + 1 b differs from that of Figure 8 in that these points are disposed on the second straight line D2 and the arrangement of the points 2a +, 2a and 2b +, 2b- differs from Figure 8 in that they are disposed on the first straight line D1. The straight lines D1 and D2 are parallel to respective sides of the rectangular planar member which can be square as shown in Figure 8.

In Figure 12, there is shown a 10g radiating device having a radiating element 1 1 g. The antenna element formed from the device advantageously has the same transmitting / receiving module in Figure 1 1. This antenna element differs from that of Figure 1 1 available lines D1 and D2 according to which extend the two quadruplets of points. In this variant, the straight lines D1 and D2 orthogonal link opposite vertices of the square.

The variants of Figures 1 1 and 12 are advantageous because they enable to realize the coupling of the eight points of excitation by means of only two slots f1 and f2 or f3, f4 extending longitudinally along the two lines D1 and D2. These antennas have the same advantages as the antenna of Figure 8 in terms of gains and polarizations.

Alternatively, the second set of points is identical to that of Figures 5 and 7: 1 a +, a- 1, 2a + 2a, 3a +, 3a, 4a + 4e. The transmission / reception circuit advantageously comprises the part 20c of the circuit of FIG 5 or FIG circuit 20d 7Who is coupled to these points. The first set of points is to when it identical to that of FIG 8: 1 + b, 1 b, 2 b + 2r. The transmission / reception circuit advantageously comprises the part of the 20th circuit of Figure 10 which is coupled to these points. This embodiment makes it possible to transmit at a high power and to limit the number of points of excitation and therefore to conductors used for detecting when the measured power is low.

Thus, in the first embodiment, each point of the first set of points is coupled to a transmit amplifier chain 10a 1 and each point of the second set is coupled to a receiver 120a amplification chain. The points of the first set are not coupled to the receiving amplifier channels and the points of the second set are not coupled to the transmit amplifier chain.

Advantageously, the excitation points are positioned and coupled to the respective amplification channels such that each amplification chain is loaded substantially by its optimal impedance. The impedance loaded onto an amplification chain is preferably the impedance of the chain formed by the radiating means, coupled to the amplifier chain at excitation point or coupled to point (s), and each line supply connecting the radiating device to the amplification chain.

In an advantageous embodiment, the impedances of the feeders are negligible so that the impedance loaded onto an amplification chain is substantially of the load formed by the radiating device to the excitation point or between the points excitation coupled (s) to the amplification chain.

Advantageously but not necessarily, to optimize the performance, the output impedance of each transmit amplifier chain coupled to one or two excitation points is substantially the conjugate of the impedance of the radiating device 10 shown in said chain emission amplification 1 or 10a at said point between said points and the input of each receiving amplifier chain impedance 120a coupled to one or two excitation points is substantially the conjugate of the impedance of the radiating device presented to reception amplification chain 120a to the point or between said points.

In Figure 13, there is shown a first example 1000 of a second antenna embodiment according to the invention. This antenna comprises a planar radiating device 10 identical to that of Figure 1. In this second embodiment, the processing module 200a includes a transmit circuit comprising a transmit circuit said high own power to deliver signals to excite the radiating element. This circuit comprises a transmitter amplifier chain high power 1 10a in Figure 1 3, to excite the radiating element and a low-power transmission circuit. 200a transmitting circuit comprises a further transmitting circuit is a transmitting circuit of said low power which is of lower power than the receiving circuit. This transmission circuit comprises a so-called emission amplification chain low power 220a. The high power transmit amplifier chain 1 10a is coupled to the first point 1 and the transmit amplifier chain low power 220a is coupled to the second point 2.

Generally applicable to all variants of the second embodiment, the processing circuit comprises a transmitting circuit of high own power to deliver high power signals to excite the radiating element, and a transmit circuit low own power to issue more low power signals to excite the radiating element, the high-power output circuit being coupled to a first set of at least one excitation point of the transmitting circuit and low-power transmission circuit being coupled to a second set of at least one excitation point. These circuits are not coupled to the same points of the first and second set. The high power transmit circuit comprises at least one chain amplification, said high power and low power transmit circuit comprises at least one amplification chain, so-called low power, of lower power than the high power amplification chain. By high power transmit amplifier chain transmitting an amplification chain means capable of delivering a higher maximum signal power a low power emission amplification chain. Each high power transmit amplifier chain is coupled to one or two points of the first set of points and each low power transmit amplifier chain is coupled to one or two points of the second set. The chains high and low power emission are not coupled to common points of the first and second set. The power ratio between the maximum power of emissions from both types of emission amplification chains may typically be up to 10 dB.

The advantage of such a solution is to allow an independent impedance matching for both types of signals (high and low power), while ensuring a summation of these signals directly to the radiating element (on the excitation points distinct) which limits energy losses.

It is possible to provide that each high power transmit amplifier chain 1 10a coupled to an excitation point so as to be adapted to excite asymmetrically (as in Figure 13) or coupled to a pair excitation point (as in the subsequent figures) so as to excite differentially is loaded on a substantially by its optimal impedance. This impedance loaded onto a high power amplification chain is the impedance of the chain formed by the radiating device coupled to the high power amplification chain excitation point or points of excitation and each line power connecting the radiating device to the amplification chain (s) point (s) corresponding excitation. This adaptation of

In an advantageous embodiment, the impedances of the feeders are negligible so that the impedance loaded onto a high power amplification chain is substantially the impedance of the radiating device to the excitation point or between the points excitation coupled to this amplifier chain.

Advantageously, in order to achieve an optimal impedance matching, high power transmission of each amplifier chain the output impedance of 1 10a is substantially the conjugate of the impedance of the radiating device 10 to the chain high power transmission amplifier to said point or between the said points making it possible to obtain a high emission efficiency, which is essential for high power in particular for thermal reasons.

Optimal output impedance of the transmission amplification channels and reception typically has an impedance of 20 Ohms. One can provide impedance matching for the signals which are potent radar signals and an impedance mismatch may be accepted between the output of a low-power power amplification chain (e.g. delivering communication signals or interference) and the excitation point to which it is coupled, the energy efficiency is less important in this case.

Alternatively, the high transmission power amplification chains and low power have optimum output impedances of distinct. We can then realize the impedance modifications described above for emission amplification chains of high power for low power transmission amplifier systems

Each of these channels comprises at least one transmission amplifier, for example a power amplifier. A high-power transmit amplifier chain comprises at least one high-power amplifier 1 14a (supplying a signal as in Figure 1) or 1 14 (from outputting a differential signal) and a transmission amplifying chain low-power comprises at least one

transmit amplifier lowest power 218 (for receiving a single-ended signal as on Ia1) or 218 (in adapted to receive a differential signal as in the following figures).

In Figure 21, there is shown in dotted lines the reflection coefficient or the steady rate wave from the feed point 1 only when this is energized, and in full lines the reflection coefficient of the same point when the points 1 and 2 are driven simultaneously by their respective emission amplification channels when the impedance of the first port module is 20 ohms, the impedance of the second section 2 is 50 ohms and the impedance Release of the second transmit amplifier chain is 500 Ohms. We note that even with this latest very high impedance, the first point of the reflection coefficient is very slightly disturbed by the excitation of the second port. The signals emitted by the two points

Advantageously, each transmit amplifier chain high power has a narrow bandwidth while the low transmission power amplification system has a large bandwidth. Indeed, high power radar signals should have a spread less wide frequency interference signals or telecommunication lower power.

The antenna according to the second embodiment may have several variants with radiating devices planes arranged as in the figures of the first embodiment and having an associated processing circuit. The transmission circuit comprises in each case two transmission circuits coupled respectively to the first and second sets of points.

The transmission circuit of each of the respective Figures 14 to 20 comprises the transmission circuit of each of the respective Figures 1 to 12 (except 6 and 9), which constitutes the high-power output circuit, coupled to the points of first set and a low-power transmission circuit coupled to the points of the second set. The low-power transmission circuit is identical to the high power transmission circuit to power close. For example, in Figure 13, the transmission circuit 200a comprises the transmitting amplifier chain 1 10a of Figure 1 which is here the high power transmit amplifier chain coupled to point 1. 200a transmitting circuit also comprises an amplification chain

The transmitting circuit 200 of the antenna 1000a of Figure 14 differs from Figure 3 in that it comprises a low-power transmit amplifier chain 220 comprising a low-power amplifier 218 coupled to the pair 6+ points 6 of the second set to excite these points symmetrically.

15 shows another variant of the antenna 1000b combining elements of Figs 13 and 14 and comprising a transmission circuit 200b.

The circuit 200c transmit antenna 1000c of FIG 1 6 differs from that of Figure 5 in that it comprises transmitting circuit A of Figure 15 coupled to the points of the first set 1 a +, a- 1 ; + 2a, 2a; 3a + 4a and 3a + 4a forming the high-power output circuit and being supplied by a SOU1 source and a low-power transmission circuit C supplied by another source SOU2. The circuit C of low-power transmission is identical to the circuit A power emission amplification chains close. The four chains of the low-power transmission circuit transmitting amplifier 231, 232, 233, 234 are coupled to respective pairs of points b 1 + b 1; 2b +, 2b-; 3b + 4b + and 3b-, 4b- the second set. The circuit C comprises transmitting in phase shifting means 225, 226 comprising at least one phase shifter for introducing a first phase shift in emission between the signal applied to the first pair 1 b +, b- 1 and the signal applied to the second pair 2b +, 2b- and introduce the same first transmission phase shift between the signal applied to the pair 3b +, 3b- and the signal applied to the pair 4b +, 4b-. The signals output by the phase shifter 225 are input channels 231 and 233 and those delivered by the phase shifter 226 are input channels 232 and 234. The phase shifters 225 and 226 receive as input a result of a same source signal SOU2 delivering a signal divided between the two phase shifters using a splitter 222. Each set of points of Figure 16 allows the transmitting eight times more power than a 1 excitation point while allowing to adapt specifically impedance between the high-power signals and low power. This configuration allows to control the polarization of the two types of high power and low transmission power independently and transmit these different powers of signals in two different directions. This solution can cover the secondary emission lobes by other issues close to the reception band but outside of this band. This allows to avoid getting scramble in the side lobes. It is a weapon against repeater jammers. specifically impedance between the high-power signals and low power. This configuration allows to control the polarization of the two types of high power and low transmission power independently and transmit these different powers of signals in two different directions. This solution can cover the secondary emission lobes by other issues close to the reception band but outside of this band. This allows to avoid getting scramble in the side lobes. It is a weapon against repeater jammers. specifically impedance between the high-power signals and low power. This configuration allows to control the polarization of the two types of high power and low transmission power independently and transmit these different powers of signals in two different directions. This solution can cover the secondary emission lobes by other issues close to the reception band but outside of this band. This allows to avoid getting scramble in the side lobes. It is a weapon against repeater jammers. transmit these different powers of signals in two different directions. This solution can cover the secondary emission lobes by other issues close to the reception band but outside of this band. This allows to avoid getting scramble in the side lobes. It is a weapon against repeater jammers. transmit these different powers of signals in two different directions. This solution can cover the secondary emission lobes by other issues close to the reception band but outside of this band. This allows to avoid getting scramble in the side lobes. It is a weapon against repeater jammers.

Advantageously, the first phase shift transmission inserted between the excitation signals of the points of the second set of points is adjustable. This phase shift may be adjustable independently of the first phase shift transmission inserted between the excitation signals of the first set of points. This phase shift is advantageously adjusted by means of the adjusting device 35.

Advantageously, the pointing phase shifting means for introducing adjustable overall phase shifts between the excitation signals applied to the points of the second sets of excitation of the respective antenna elements of the antenna points. For example, the controller 36 generates a control signal SC including global signals controlling the introduction of the overall phase shifts of the signals input to each phase shifter.

1000d The antenna of Figure 17 differs from that of Figure 1 6 by the transmitting circuit 200d. The transmission circuit 200d comprises a high power transmit circuit Ad identical to that of Figure 7. The transmission circuit 200d comprises a low Bd identical transmission power circuit Ad circuit to the powers near and connected the points of the second set of points. This circuit comprises four Bd lower power transmit amplifier chains 231, 232, 233, 234 that the chains 21, 22, 23 and 24 and being respectively connected to pairs of points b 1 + b 1; 2b +, 2b-; 3b + 4b + and 3b-, 4b- the second set. phase shifting means used to introduce a first phase shift in emission between the excitation signals applied to the pairs of points

These phase shift means comprises four phase shifters 127a,

127b, 128a, 128b. The two phase shifters 127a and 127b each receive a

signal from the same source SO3, apply respective phase shifts to this signal and outputs the input signals of the channels 231 and 232. The two phase shifters 128a and 128b each receive a signal from the same source SO4, apply phase shifts this signal and deliver the input signals of the channels 233 and 234. the signals from the sources SO3 and SO4 pass through respective splitters 222a and 222b before being injected at the input of the phase shifters 127a, 127b, 128a, 128b.

The phase shifts introduced between the excitation signals applied to pairs b + 1, 1 + b and 2b, and between the pairs 2b- 3b +, 3b- + and 4b, 4b-may be identical. Alternatively such signals may be different. This allows to transmit and receive two waves with polarizations may be different by means of the second set of points.

Advantageously, the phase shifts are adjustable.

The phase shifts introduced between the transmitting signals applied to the pairs of points b + 1, 1 + b and 2b, 2b- and between the signals applied to pairs 3b +, 3b- and 4B +, 4b- may advantageously be independently controlled. It is then possible to independently adjust the polarizations of elementary waves emitted by the first quadruplet points 1 b + 1 b, 2b + 2b- and the second quadruplet points 3b +, 3b-, 4b +, 4b- the second set.

Advantageously, said score phase shifting means used to introduce the first overall phase shifts between the excitation signals applied to the excitation signals of the first quadlet of points 1 b + 1 b, 2b + 2b- second sets of respective antenna elements and second adjustable overall phase shifts between the excitation signals of the second quadruplets points 3b +, 3b-, 4b +, 4b- second sets respective elementary antennas of the array, the first and second overall phase shifts applied to the signals excitation second sets may be different. It is then possible to simultaneously transmit four beams in four different directions through two sets of points. Examples which may be two radar signals in two different directions and / or with different polarizations two interference signals in two different directions and / or with different polarizations. One can for example make communication in a band, protecting lobes and diffuse and also two assets radar brushes in different directions. One can also have programming in different polarizations or polarization agility in the show.

Advantageously, the overall phase shifts in transmission and / or reception are adjustable.

Advantageously, the overall phase shifts applied to the two sets of points are independently adjustable. pointing directions are adjustable independently.

In the nonlimiting example of FIG 17, the pointing phase shift means comprises the control device 36 generates a control signal SC comprising various signals controlling the introduction of the aforementioned phase shifts (global and non-global) to be applied to the signals received at the input of the various phase shifters and transmits these signals to the adjusting device 35 so that it controls the phase shifter for these phase shifts they introduce on the signals they receive.

The embodiment of Figure 18 differs from that of Figure 1 6 that the radiating element 1 1 e of the 10th radiating device includes a first set of points including only the first quadlet of points 1 a +, a- 1, + 2a and 2a and a second set of points including only the first quadlet of points b + 1, 1 + b and 2b and 2R. The 200th transmitting circuit associated differs from that of Figure 1 6 that it comprises only part of the processing circuit coupled to the excitation points. Figures 19 and 20 differ from the embodiment of Figure 18 by the provisions of excitation identical to those of Figures 8 and respectively 10. A provision of the excitation points as in Figure 1 1 is also conceivable.

Figures 13 et seq, for clarity, shows only the receiving circuit. The antenna may also comprise a receiving circuit. Each point or pair of points may be coupled to a receiving amplifier chain in addition to the transmit amplifier chain for processing signals from the point or the point pair. Means for receiving in phase shift may be provided to ensure phase shifts between the signals from the same points as the phase shifts introduced by the phase shift in emission means on the excitation signals. This sets the polarizations of the received signals. Means for introducing the overall phase shifts in reception may

also be provided so as to allow changing the receiving pointing direction.

Alternatively, the second set of points is identical to that of Figures 5 and 7: 1 a +, a- 1, 2a + 2a, 3a +, 3a, 4a + 4e. The transmitting circuit advantageously comprises the part of the circuit 200c in Figure 16 or 200d circuit of Figure 17 which is coupled to these points. The first set of points is to when it identical to that of FIG 20: 1 + b, 1 b, 2 b + 2r. The transmitting circuit advantageously comprises the part of the 200th circuit of Figure 20 which is coupled to these points.

Thus, in the second embodiment, each point of the first set of points is coupled to a high power transmit amplifier chain and each point of the second set is coupled to a lower transmit amplifier chain power. The points of the first set are not coupled to the amplification channels of low transmission power and the points of the second set are not coupled to the high power transmission amplifier systems.

The processing circuits are advantageously made MMIC technology. Preferably, a SiGe (Silicon Germanium) is used. Alternatively, a GaAs technology is used (Gallium Arsenide) or GaN (Gallium Nitride). Advantageously, the transmission amplification chains and receiving the same antenna element are formed on a same substrate. The congestion is reduced and the integration of the amplification in the rear channels of the planar radiating device 10 is facilitated.

Advantageously, in embodiments not limited to those shown in the figures, each of the first type amplification channel is connected to an amplification chain of the second type. These amplification chains are coupled to respective excitation points. The excitation points are distributed so that the two chains associated amplifications with each other are intended to transmit or receive, by the respective excitation points of the respective polarized elementary waves linearly in the same direction. In other words, this direction is common to the two amplifier. In other words, each of the amplification channels connected to one another is coupled to a set of at least one point

a polarized wavelet linearly in one direction. This direction is the same for the two amplification chains coupled to one another.

This configuration allows the antenna element to transmit and simultaneously detecting a total wave linearly polarized in the same direction or emit polarized waves simultaneously total linearly in the same direction by means of both types of amplification channels without shifters. However, this mode is the most common. We can, for example, remove the phase shifters figures of embodiments. In other words, the amplification chains may be devoid of phase shifters which limits the cost and volume of the antenna element and an integration gain.
Each amplification channel is coupled to a single excitation point for asymmetric excitation or torque excitation points for differential excitation.
In Figures 1 to 4 and 13 to 15, these excitation points are arranged so as to all be on one of D1 or D2 lines. Where an amplification system is coupled to two excitation points, these points are arranged symmetrically with respect to the center C. The detected polarizations or emitted by these points are linearly polarized along the line on which are arranged points.
Figures 1 1 to 12 and 20, the excitation points are arranged so as to all lie on the lines D1 and D2. Where an amplification system is coupled to two excitation points, these points are arranged symmetrically with respect to the center C. The two points of the same pair are arranged on the same straight line and are intended to emit or detecting a polarized wavelet rectilinearly this line.

CLAIMS
1. Elementary antenna comprising a planar radiating device comprising a substantially planar radiating element and a transmission and / or reception circuit comprising at least an amplification chain of a first type and at least one amplification chain of a second type , each amplification chain of the first type being coupled to at least one excitation point of a first set of at least one excitation of the radiating element point and each amplification chain of the second type being coupled to at least one point of a second set of excitation of the radiating element points, excitation of the first and second set points being distinct, and the amplification system of the first type being different from the chain
2. Elementary antenna according to the preceding claim, wherein the excitation points of the first set and the second set having different impedances.
3. Elementary antenna according to any preceding claim, comprising a transmission and reception circuit, said circuit comprises:
- at least one own transmit amplifier chain to provide signals for energizing the radiating element, each transmit amplifier chain being coupled to at least one point of the first set of at least one point excitation of said radiating element; - at least one own reception amplification system for amplifying signals from the radiating element, each receiving amplifier chain being coupled to at least one point of the second set of at least one excitation point of said element beaming.
4. Elementary antenna according to the preceding claim, wherein the excitation points are positioned and coupled to the respective amplification channels such that each amplification chain is loaded substantially by its optimal impedance, the impedance loaded onto each chain amplification being the impedance of the chain formed by the radiating device coupled to the amplification chain and each feed line coupling the radiating device to the amplification chain.
5. Elementary antenna according to the preceding claim, wherein:
- at least a transmit amplifier chain coupled to a point or two points in the first set has an output impedance that is substantially conjugate with an impedance of the radiating device presented to said emission of said amplification system point or between the two points of the first set,
And or
- at least one receiving amplifier chain coupled to a point or two points in the first set has an output impedance substantially conjugate with an impedance of the radiating device presented in said amplification chain or receiving said point between the two points of the second set.
6. Elementary antenna according to any one of claims 1 to 2, comprising a transmission circuit, the transmission circuit comprising:
- at least a said transmit amplifier chain high own power providing signals for energizing the radiating element, each high power transmit amplifier chain being coupled to at least one point of the first set at least one excitation point of said radiating element;
- at least a second said emission amplifier chain low power, lower than the first power amplifying power chain, adapted to deliver signals to excite the radiating element, each channel of amplification 'low power transmission being coupled to at least one point of the second set of at least one excitation point of said radiating element.
7. Elementary antenna according to the preceding claim, wherein the excitation points are positioned and coupled to each chain
emitting high power amplification so that each high power amplifier chain is loaded substantially by its optimal impedance, the impedance loaded onto each high power amplification chain being the impedance of the chain formed by the radiating device coupled to the amplifier and each feed line coupling the radiating device to the high power emission amplification system chain.
8. Elementary antenna according to the preceding claim, wherein at least one high power emission amplification chain coupled to a point or two points in the first set has an output impedance that is substantially conjugate with an impedance of the device radiating presented at said point of said transmit amplifier or between the two points of the first set chain.
9. Elementary antenna according to any preceding claim, wherein the impedance of each of the first set of excitation point is less than the impedance of each excitation of the second set item.
10. Elementary antenna according to any preceding claim, wherein each amplifier chain of the first type is associated with an amplification chain of the second type, these amplification channels being coupled to the excitation points arranged to transmitting or receiving respective elementary waves linearly polarized in the same direction.
January 1. Elementary antenna according to any preceding claim, wherein the radiating element is defined by a first straight line (D1) passing through a central point (C) of the radiating element and a second right (D2) perpendicular to the first right (D1) and passing through the central point (C), the excitation points being distributed only on the first and / or the second straight line.
12. Elementary antenna according to the preceding claim, wherein the excitation points are distributed only on the first and on the second straight line, the radiating device comprising two slots extending longitudinally along the first straight line (D1) and the second straight line ( D2), the two slots ensuring the coupling of all the excitation points.
13. Elementary antenna according to any preceding claim, wherein at least one set selected from the first set (1 a +, a- 1, 2a + 2a) and the second set (b 1 + b 1, 2b + , 2b-) comprises at least a pair of the excitation points, the pair of excitation points comprising two excitation points coupled to the transmitting circuit and / or reception such that a differential signal is intended for use between the radiator and the transmission circuit.
14. Elementary antenna according to the preceding claim, wherein at least one set from among the first set and the second set comprises a first quadruple of the excitation points, the radiating element being defined by a first straight line (D1) passing through a center (C) of the radiating element and a second right (D2) perpendicular to the first straight line (D1) and passing through the center (C), the excitation points of each first quadruplet of points of excitation comprise a first pair of excitation dots composed of excitation points (1 a +, a- 1, b + 1, 1 b) disposed substantially symmetrically with respect to said first straight line (D1) and a second pair of excitation point composed of pointsexcitation disposed substantially symmetrically with respect to said second straight line (D2).
15. Elementary antenna according to the preceding claim, wherein the excitation points of the first quadruplet points are located at a distance from the first right (D1) and the second right (D2).
16. Elementary antenna according to claim 14, wherein each assembly comprises a first quadruplet excitation points located on the first straight line (D1) and the second right (D2).
17. Elementary antenna according to claim 14, wherein each set consists of a first quadruplet points, the excitation points of each first quadruplet points being situated on one side of a third straight line (D3) located in the plane defined by the radiating element, passing through the central point (C) and being a bisector of the angle formed by the first and the second straight line.
18. Elementary antenna according to any one of claims 14 to 16, wherein said assembly comprises a second quadruple of excitation points away from the first right (D1) and the second right (D2) comprising:
a third pair consisting of the excitation points (3a +, 3e) arranged substantially symmetrically with respect to said first straight line (D1), the points of the third pair of points (3a +, 3a) being arranged on the other side the second right (D2) with respect to the first pair of excitation points (1 + a, 1 e) of said assembly,
a fourth pair consisting of the excitation points (4a +, 4a) arranged substantially symmetrically with respect to said second straight line (D2), the points of the fourth pair of points (4a +, 4a) being disposed on the other side the first right (D1) relative to the second pair of excitation points (1 a +, a- 1) of said set.
19. Elementary antenna according to the preceding claim, wherein each set from among the first set and the second set includes a first and a second quadruplets points.
20. Elementary antenna according to any one of claims 18 to 19, including phase shifting means for introducing a first phase difference between a first signal applied, or derived from, the first pair of excitation points and a second applied signal on, or derived from, respectively, the second pair of excitation and a second phase shift of said set points may be different from the first phase difference between a third signal applied to, or derived from, respectively, the third pair or from the third pair excitation points of said assembly and a fourth signal applied to, or derived from, respectively, the fourth pair of excitation of said set points.
21. Elementary antenna according to any one of claims 18 to 20, the first quadlet of points and the second points of quadruplet at least one assembly being excited by means of different frequency signals or being summed separately.
22. An antenna comprising a plurality of elementary antennas according to any preceding claim, wherein the radiating elements form an array of radiating elements.
23. Antenna according to the preceding claim in that it depends on claim 18, comprising scoring phase shifting means make it possible to introduce the first overall phase shifts between the signals applied to, or derived from, the first quadlet of points at least one set of points of the respective antenna elements and second overall phase shifts between the signals applied to the, or respectively from the, second quadruplets points of said set of points of the respective antenna elements, the first and second global phase offsets can be different.