Claims:STATEMENT OF CLAIMS
We Claim:
1. A method for performing a sampling Clock Offset (SCO) estimation in a wireless communication network, the method comprising:
estimating a phase-shift corresponds to a timing drift by processing a received signal in a frequency domain, wherein the timing-drift corresponds to a clock timing offset between a transmitting station and a receiving station; and
estimating the SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain, wherein the phase-shifted correlation vector is computed with various time-drift values and the phase-shifted correlation vector corresponds to a particular time-drift.
2. The method of claim 1, wherein the received signal corresponds to one of a Primary Synchronization Signal (PSS), a Secondary Synchronization Signal (SSS), and a reference signal.
3. The method of claim 2, wherein the SCO corresponding to the PSS is estimated by:
correlating a received PSS channel transfer function with a phase-shifted correlation vector in the frequency domain, wherein a phase shift at which a correlation maximum value is determined as the SCO.
4. The method of claim 2, wherein the SCO corresponding to the SSS is estimated by:
correlating a received SSS channel transfer function with a phase-shifted correlation vector in the frequency domain, wherein the phase shift at which a correlation maximum value is determined as the SCO.
5. The method of claim 2, wherein the SCO corresponding to the reference signal is estimated by:
correlating a received reference symbol channel transfer function with a phase-shifted correlation vector in a frequency domain, wherein the phase shift at which a correlation maximum value is determined as the SCO.
6. The method of claim 2, wherein output of the SCO estimation includes an integer SCO and a fractional SCO.
7. The method of claim 6, wherein the integer SCO is corrected by one of retarding or advancing time samples after an Analog-to-Digital Converter (ADC).
8. The method of claim 6, wherein the fractional SCO is corrected by interpolating time sequence.
9. An apparatus for performing a sampling Clock Offset (SCO) estimation in a wireless communication network, the apparatus comprising a SCO estimating unit configured to:
estimate a phase-shift corresponds to a timing drift by processing a received signal in a frequency domain, wherein the timing-drift corresponds to a clock timing offset between a transmitting station and a receiving station; and
estimate the SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain, wherein the phase-shifted correlation vector is computed with various time-drift values and the phase-shifted correlation vector corresponds to a particular time-drift.
10. A computer program product comprising a computer executable program code recorded on a computer readable non-transitory storage medium, wherein said computer executable program code when executed causing the actions including:
estimating a phase-shift corresponds to a timing drift by processing a received signal in a frequency domain, wherein the timing-drift corresponds to a clock timing offset between a transmitting station and a receiving station; and
estimating a Sampling Clock Offset (SCO) by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain, wherein the phase-shifted correlation vector is computed with various time-drift values and the phase-shifted correlation vector corresponds to a particular time-drift.

Dated this 20th Day of February, 2017 Signatures:

Arun Kishore Narasani
Patent Agent
, Description:FIELD OF INVENTION
[0001] The embodiments herein relate to a wireless communication network, and more specifically to a method and apparatus for performing a Sampling Clock Offset (SCO) estimation in a wireless communication network.
BACKGROUND OF INVENTION
[0002] Conventionally, SCO estimation is performed in a time domain after in-phase (I) and quadrature phase (Q) samples are received from an Analog to Digital Converter (ADC). This estimation depends on time domain samples by discovering early or late arrival of the samples based on a reference threshold. Various methods (e.g., squaring loop method, early or late gate recovery correlation method, spectral correlation method, or the like) are used to estimate the SCO. Further, the estimation of the SCO is performed in a frequency domain also. In the frequency domain, the existing methods are mainly based on a correlation or signal processing of a reference symbol (containing known pilot subcarriers) arriving at time T0 with another reference symbol (containing pilot subcarriers) subsequently arriving at T1 are compared or correlated and processed to find a timing clock shift.
[0003] The above information is presented as background information only to help the reader to understand the present invention. Applicants have made no determination and make no assertion as to whether any of the above might be applicable as Prior Art with regard to the present application.
OBJECT OF INVENTION
[0004] The principal object of the embodiments herein to provide a method and apparatus for performing a SCO estimation in a wireless communication network.
[0005] Another object of the embodiments herein is to estimate a phase-shift corresponding to a timing drift by processing a received signal in a frequency domain.
[0006] Another object of the embodiments herein is to provide the timing-drift corresponding to a clock timing offset between a transmitting station and a receiving station.
[0007] Another object of the embodiments herein is to compute a phase-shifted correlation vector based on various time-drift values.
[0008] Another object of the embodiments herein is to estimate the SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain.
SUMMARY
[0009] Embodiments herein disclose a method for performing a SCO estimation in a wireless communication network. The method includes estimating a phase-shift corresponds to a timing drift by processing a received signal in a frequency domain. The timing-drift corresponds to a clock timing offset between a transmitting station and a receiving station. Further, the method includes estimating the SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain.
[0010] In an embodiment, the phase-shifted correlation vector is computed with various time-drift values and the phase-shifted correlation vector corresponds to a particular time-drift.
[0011] In an embodiment, the received signal corresponds to a Primary Synchronization Signal (PSS).
[0012] In an embodiment, the received signal corresponds to a Secondary Synchronization Signal (SSS).
[0013] In an embodiment, the received signal corresponds to a reference signal.
[0014] In an embodiment, the SCO corresponding to the PSS is estimated by correlating a received PSS channel transfer function with a phase-shifted correlation vector in the frequency domain. A phase shift at which a correlation maximum value is determined as the SCO.
[0015] In an embodiment, the SCO corresponding to the SSS is estimated by correlating a received SSS channel transfer function with a phase-shifted correlation vector in the frequency domain. The phase shift at which a correlation maximum value is determined as the SCO.
[0016] In an embodiment, the SCO corresponding to the reference signal is estimated by correlating a received reference symbol channel transfer function with a phase-shifted correlation vector in a frequency domain. The phase shift at which a correlation maximum value is determined as the SCO.
[0017] In an embodiment, an output of the SCO estimation includes an integer SCO and a fractional SCO.
[0018] In an embodiment, the integer SCO is corrected by one of retarding or advancing time samples after an Analog-to-Digital Converter (ADC).
[0019] In an embodiment, the fractional SCO is corrected by interpolating time sequence.
[0020] Embodiments herein disclose an apparatus for performing a SCO estimation in a wireless communication network. The apparatus includes an estimating unit configured to estimate a phase-shift corresponds to a timing drift by processing a received signal in a frequency domain. The timing-drift corresponds to a clock timing offset between a transmitting station and a receiving station. The estimating unit is further configured to estimate the SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain. The phase-shifted correlation vector is computed with various time-drift values. The phase-shifted correlation vector corresponds to a particular time-drift.
[0021] Embodiment herein provides a computer program product including a computer executable program code recorded on a computer readable non-transitory storage medium. The computer executable program code when executed causing the actions include estimating a phase-shift corresponds to a timing drift by processing a received signal in a frequency domain. The timing-drift corresponds to a clock timing offset between a transmitting station and a receiving station. The computer executable program code when executed causing the actions include estimating a SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain. The phase-shifted correlation vector is computed based on various time-drift values. The phase-shifted correlation vector corresponds to a particular time-drift.
[0022] These and other aspects of the embodiments herein will be better appreciated and understood when considered in conjunction with the following description and the accompanying drawings. It should be understood, however, that the following descriptions, while indicating preferred embodiments and numerous specific details thereof, are given by way of illustration and not of limitation. Many changes and modifications may be made within the scope of the embodiments herein without departing from the spirit thereof, and the embodiments herein include all such modifications.
BRIEF DESCRIPTION OF FIGURES
[0023] This invention is illustrated in the accompanying drawings, throughout which like reference letters indicate corresponding parts in the various figures. The embodiments herein will be better understood from the following description with reference to the drawings, in which:
[0024] FIG. 1 illustrates an overview for SCO estimation and compensation in a 3rd Generation Partnership Project Long Term Evolution (3GPP LTE) system, according to the embodiments as disclosed herein;
[0025] FIG. 2 illustrates various units of an apparatus for performing the SCO estimation in a wireless communication network, according to the embodiments as disclosed herein;
[0026] FIG. 3 is a flow diagram illustrating a method for performing the SCO estimation in the wireless communication network, according to the embodiments as disclosed herein; and
[0027] FIG. 4 illustrates a computing environment implementing a mechanism for performing the SCO estimation in the wireless communication network, according to the embodiments as disclosed herein.

DETAILED DESCRIPTION OF INVENTION
[0028] The embodiments herein and the various features and advantageous details thereof are explained more fully with reference to the non-limiting embodiments that are illustrated in the accompanying drawings and detailed in the following description. Descriptions of well-known components and processing techniques are omitted so as to not unnecessarily obscure the embodiments herein. Also, the various embodiments described herein are not necessarily mutually exclusive, as some embodiments can be combined with one or more other embodiments to form new embodiments. The term “or” as used herein, refers to a non-exclusive or, unless otherwise indicated. The examples used herein are intended merely to facilitate an understanding of ways in which the embodiments herein can be practiced and to further enable those skilled in the art to practice the embodiments herein. Accordingly, the examples should not be construed as limiting the scope of the embodiments herein.
[0029] As is traditional in the field, embodiments may be described and illustrated in terms of blocks which carry out a described function or functions. These blocks, which may be referred to herein as units or modules or the like, are physically implemented by analog or digital circuits such as logic gates, integrated circuits, microprocessors, microcontrollers, memory circuits, passive electronic components, active electronic components, optical components, hardwired circuits, or the like, and may optionally be driven by firmware and/or software. The circuits may, for example, be embodied in one or more semiconductor chips, or on substrate supports such as printed circuit boards and the like. The circuits constituting a block may be implemented by dedicated hardware, or by a processor (e.g., one or more programmed microprocessors and associated circuitry), or by a combination of dedicated hardware to perform some functions of the block and a processor to perform other functions of the block. Each block of the embodiments may be physically separated into two or more interacting and discrete blocks without departing from the scope of the invention. Likewise, the blocks of the embodiments may be physically combined into more complex blocks without departing from the scope of the invention
[0030] Embodiments herein provide a method for performing a SCO estimation in a wireless communication network. The method includes estimating a phase-shift corresponds to a timing drift by processing a received signal in a frequency domain. The timing-drift corresponds to a clock timing offset between a transmitting station and a receiving station. Further, the method includes estimating the SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain.
[0031] The proposed method can be implemented in a 3GPP LTE and LTE Advanced like Release-8, Release 9, Release 10, Release 11, Release 12 and beyond standards for effectively estimating and compensating the SCO. The implementation of the proposed method is not only limited to the LTE system but also be extended to any Orthogonal Frequency Division Multiplexing (OFDM) based wireless systems.
[0032] Unlike the conventional methods, the proposed method effectively estimates and compensates the SCO. The proposed method provides a robustness performance against multipath fading and Doppler Spread in a Single Input Single Output (SISO), Single Input Multiple Output (SIMO), Multiple Input Single Output (MISO) and Multiple Input Multiple Output (MIMO) techniques.
[0033] Referring now to the drawings, and more particularly to FIGS. 1 through 4, there are shown preferred embodiments.
[0034] FIG. 1 illustrates an overview for SCO estimation and compensation in a 3GPP LTE system, according to the embodiments as disclosed herein. The SCO occurs due to an Analog-to-Digital Converter (ADC) clock frequency differences between a transmitting station and a receiving station. During the downlink (DL) situation in the LTE system, the transmitting station is evolved NodeB (eNodeB) and a receiving station is User Equipment (UE), whereas during the UL situation in the LTE system, the transmitting station is the UE and the receiving station is the eNodeB.
[0035] The SCO estimation and compensation of the time-drift in received ADC IQ samples in the OFDM system is important for synchronization of the receiving station with respect to the timing of the transmitting station. In an example, in the LTE system, the SCO is used to perform high speed DL and UL data reception and transmission using the OFDM technology. The SCO is defined in parts per million (ppm) and is based on the quality of clock oscillators in a Radio Frequency (RF) and a mixed-signal circuitry. If the ppm is high, the clock offset is more. Therefore, a synchronization of the SCO is an important factor that needs to be corrected for a practical OFDM system.
[0036] In an embodiment, one or more pilot symbol(s) in the frequency domain is processed for SCO estimation.
[0037] In an embodiment, in the LTE system, a PSS, a SSS and a RS signal in the frequency domain are processed for estimating a phase-shift which corresponds to a timing-drift in the time-domain. The estimated time-drift represents the clock timing offset between the transmitting station and the receiving station. Further, an output of the SCO is split into in two parts (i.e., integer SCO and fractional SCO). The integer SCO and fractional SCO are computed in a single processing block as shown in the FIG. 1.
[0038] In an embodiment, the integer SCO is corrected by retarding or advancing the time samples after the ADC.
[0039] In an embodiment, the fractional SCO is corrected by interpolating the time-sequence using at least one of a linear method, a cubic method, a spline method or the like. The corrected signal is further processed for downlink physical channels processing like Physical broadcasting channel (PBCH), Physical control format indicator channel (PCFICH), Physical HARQ indicator channel (PHICH), Physical downlink control channel (PDCCH) and Physical downlink shared channel (PDSCH).
[0040] In an embodiment, an apparatus is used for performing the SEO estimation in the LTE system. In an embodiment, the apparatus is the receiving station. In an embodiment, the apparatus is the transmitting station. Further, the apparatus is configured to estimate the phase-shift corresponds to the timing drift by processing the received signal in the frequency domain. The functionalities and operations of the apparatus are explained in conjunction with the FIG. 2. The timing-drift corresponds to a clock timing offset between the transmitting station and the receiving station. Further, the apparatus is configured to estimate the SCO by applying correlation of a channel transfer function of the received signal with a phase-shifted correlation vector in the frequency domain.
[0041] In an embodiment, the phase-shifted correlation vector is computed based on various time-drift values. The phase-shifted correlation vector corresponds to a particular time-drift.
[0042] In an embodiment, the received signal corresponds to the PSS.
[0043] In an embodiment, the received signal corresponds to the SSS.
[0044] In an embodiment, the received signal corresponds to the reference signal.
[0045] In an embodiment, the SCO corresponding to the PSS is estimated by correlating a received PSS channel transfer function with a phase-shifted correlation vector in the frequency domain. A phase shift at which a correlation maximum value is determined as the SCO.
[0046] In an embodiment, the SCO corresponding to the SSS is estimated by correlating a received SSS channel transfer function with a phase-shifted correlation vector in the frequency domain. The phase shift at which a correlation maximum value is determined as the SCO.
[0047] In an embodiment, the SCO corresponding to the reference signal is estimated by correlating a received reference symbol channel transfer function with a phase-shifted correlation vector in a frequency domain. The phase shift at which a correlation maximum value is determined as the SCO.
[0048] In an embodiment, an output of the SCO estimation includes the integer SCO and the fractional SCO.
[0049] In an embodiment, the integer SCO is corrected by one of retarding or advancing time samples after an Analog-to-Digital Converter (ADC).
[0050] In an embodiment, the fractional SCO is corrected by interpolating time sequence.
[0051] In an embodiment, the estimation of the SCO is performed in a digital frequency domain, that means, processing of post ADC I (in phase) and Q (quadrature phase) samples. The IQ samples are either advanced or retarded in the time based on the integer time offset TI and interpolated based on the TF fractional time offset outputting from a sampling offset estimator as shown in the FIG. 1. TI is in multiples of sample duration (or sampling time) and TF is a fraction of sample duration. In an example, if the sampling rate of IQ signals is Ts then the TI is integer multiples of Ts and TF is the fraction of Ts.
[0052] In ideal case, the received OFDM signal in the frequency domain without sampling clock offset is represented by

[0053] The index represents the time domain sample index, the index represents the subcarrier or frequency or RE index. The received signal in the presence of a fixed clock frequency error between the receiving station and the transmitting station due to the DAC clock at the transmitting station and ADC clock at the receiving station is represented by:

[0054] The above equation is writing in another way,

[0055] The is the relative frequency error. The presence of , that is , makes the subcarriers non-orthogonal and cause an Inter Carrier Interference (ICI).
[0056] The where , is integer time offset and is fractional time offset. The estimation and compensation of the or is explained below in the context of the OFDM system in the LTE, however, without limitation the proposed method is applicable for all pilot-aided or data-aided synchronization of the OFDM symbols.
[0057] The proposed method is provided based on a correlation search for best match (i.e., highest correlation peak) between the present in the received PSS and/or received SSS and/or received RS (frequency interpolated to full bandwidth (BW)) frequency subcarriers and the transfer function (frequency domain channel estimation function) obtained as and/or and/or respectively. The channel transfer function for PSS, SSS and RS are obtained by a zero-forcing channel estimation or a per-tone channel estimation in the OFDM system. The are obtained as the ratio of the received frequency domain samples at known locations to the ideal frequency domain samples at known locations. That is, it is provided as:

[0058] where is received frequency domain IQ values at known frequency locations (frequency indices) and is ideal frequency domain IQ values known to the receiving station a priori. Similarly transfer functions for SSS and RS symbols are calculated as and .
[0059] Full or part of the and subcarriers are processed for the correlation search. In an example, the central 62 REs of transfer functions of the PSS, SSS and RS ( and ) are sufficient for processing. The correlation processing of and with phase delayed vector (time drift vector) is presented in the proposed method. The correlation vector is created with various timing drift values (phase-shift) such that there is a collection of several such vectors where each vector corresponds to a particular time-drift (phase-shift).
[0060] Without limitation and processing will provide the estimation of or .
[0061] The and are estimated from the knowledge of received , and ideal sequences known the priori, that means, knowledge of required for calculating and .
[0062] The and represent the 62 REs which are present around the center DC component in the frequency spectrum. After Fast Fourier Transform (FFT) and de-mapping of the REs, the total number of non-zero REs are less than the FFT length. In an example, if the FFT length 2048 for 20MHz transmission bandwidth then the non-zero subcarriers after demapping are 1200 REs. The central PSS and SSS correspond to the REs numbering 570, 571,…631 total to 62 REs. The PSS and SSS are present only in the predefined subframes in the LTE transmission, for example, the PSS is present in the 7th OFDM symbol of subframe number 0 and 5 of every frame in the FDD, the SSS is present in the 6th OFDM symbol of subframe number 0 and 5 of every frame in FDD. The RS signals are present in 0, 4, 7 11th OFDM symbols of every subframe. The processing blocks are programmed such that they pick these REs from the received OFDM symbols in the frequency domain. The and are estimated as explained above. The processing of for estimating the is explained below.
[0063] Step 1: The method includes setting the range of sampling offset search over which the integer and fractional parts are to be estimated. In an example, consider is the search range and step size is 0.001 then the search grid is (-10,-9.999,-9.998,…,0,…,+9.998,+9.999,+10). corresponds to -10 and corresponds to +10. In another example, the corresponds to integer offset -9 and fractional offset -0.998. The value -9, for example, indicates that the received IQ samples are lagging 9 samples compared to the transmitting IQ samples.
[0064] Form the set of vectors corresponding to the above search range where as follows.
[0065] Step 2: The method includes constructing the correlation vector where for every timing offset in the .
[0066] Step 3: The method includes calculating the correlation between and , where as for .
[0067] For each search point in the above grid the result is represented as
, where represents the RE index.
[0068] Further, the method includes performing the above for the search grid where the following results are obtained.
[0069] Further, the method includes obtaining the from the sequence . The indicates the combined integer and fractional time-offset . The estimate is partitioned into integer part and fractional part and respectively.
[0070] The and are fed back to the buffer, where IQ samples are retarded or advanced by number of samples indicated by and the polarity of as positive indicates that the samples are to be retarded by samples and negative polarity indicates that the samples are to be advanced by samples. is the fractional part of time offset and is fed to an interpolation filter. The interpolation filter interpolates the received IQ samples by reconstructing the samples with respect to the fractional time-offset position indicated by the input . The fractional interpolation can be based on at least one of Lagrange method, Linear method, Cubic method, Spline method or Farrow filtering method.
[0071] The estimation of and are performed using and in the same way using the SSS and RS symbols respectively in the LTE signals. The estimated and are used to regularly update by retarding the samples and interpolating the OFDM symbols in the time-domain so as to compensate the SCO for smooth processing of the OFDM symbols.
[0072] In an embodiment, the range of search grid for desired Integer value of SCO and fractional value of SCO, the length of correlation sequences for PSS, SSS and RS symbols can vary based on accuracy of estimation of the SCO and computational complexity required by a processing system.
[0073] In an embodiment, the proposed method is performed in a data-aided mechanism in the LTE system and the OFDM based system in a frequency domain post FFT.
[0074] The FIG. 1 shows the limited overview of the system but, it is to be understood that other embodiments are not limited thereto. Further, the system can include any number of hardware or software components communicating with each other.
[0075] FIG. 2 illustrates various units of the apparatus 200 for performing the SCO estimation in the wireless communication network, according to the embodiments as disclosed herein. The wireless communication network can be, for example but not limited to, the OFDM system, an Orthogonal Frequency Division Multiple Access (OFDMA) system, a Single Carrier Frequency Division Multiple Access (SCFDMA) system, the LTE system or the like.
[0076] In an embodiment, the apparatus 200 includes a signal processing unit 202, a correlation unit 204, and a SEO estimation unit 206. The signal processing unit 202 is configured to process the received signal in the frequency domain. After processing the received signal in the frequency domain, the SEO estimation unit 206 is configured to estimate the phase-shift corresponds to the timing drift. The timing-drift corresponds to the clock timing offset.
[0077] Based on estimating the phase-shift corresponds to the timing drift, the correlation unit 204 is configured to apply correlation of the channel transfer function of the received signal with the phase-shifted correlation vector in the frequency domain. Further, the SEO estimation unit 206 is configured to estimate the SCO.
[0078] Although FIG. 2 shows exemplary units of the apparatus 200, in other implementations, the apparatus 200 may include fewer components, different components, differently arranged components, or additional components than depicted in the FIG. 2. Additionally or alternatively, one or more components of the apparatus 200 may perform functions described as being performed by one or more other components of the apparatus 200.
[0079] FIG. 3 is a flow diagram 300 illustrating a method for performing the SCO estimation in the wireless communication network, according to the embodiments as disclosed herein. At step 302, the method involves processing the received signal in the frequency domain. In an embodiment, the method allows the signal processing unit 202 to process the received signal in the frequency domain. At step 304, the method involves estimating the phase-shift corresponds to the timing drift. In an embodiment, the method allows the SEO estimation unit 206 to estimate the phase-shift corresponds to the timing drift. At step 306, the method involves applying correlation of the channel transfer function of the received signal with the phase-shifted correlation vector in the frequency domain. In an embodiment, the method allows the correlation unit 204 to apply correlation of the channel transfer function of the received signal with the phase-shifted correlation vector in the frequency domain. At step 308, the method involves estimating the SCO. In an embodiment, the method allows the SEO estimation unit 206 to estimate the SCO.
[0080] The various actions, acts, blocks, steps, and the like in the flow diagram 300 may be performed in the order presented, in a different order or simultaneously. Further, in some embodiments, some actions, acts, blocks, steps, and the like may be omitted, added, modified, skipped, and the like without departing from the scope of the invention.
[0081] FIG. 4 illustrates a computing environment 402 implementing a mechanism for performing the SCO estimation in the wireless communication network, according to embodiments as disclosed herein. The computing environment 402 comprises at least one processing unit 408 that is equipped with a control unit 404, an Arithmetic Logic Unit (ALU) 406, a memory 410, a storage unit 412, a plurality of networking devices 416 and a plurality Input/ Output (I/O) devices 414. The processing unit 408 is responsible for processing the instructions of the technique. The processing unit 408 receives commands from the control unit 404 in order to perform its processing. Further, any logical and arithmetic operations involved in the execution of the instructions are computed with the help of the ALU 406.
[0082] The overall computing environment 402 can be composed of multiple homogeneous or heterogeneous cores, multiple CPUs of different kinds, special media and other accelerators. The processing unit 408 is responsible for processing the instructions of the technique. Further, the plurality of processing units 404 may be located on a single chip or over multiple chips.
[0083] The technique comprising of instructions and codes required for the implementation are stored in either the memory unit 410 or the storage 412 or both. At the time of execution, the instructions may be fetched from the corresponding memory 410 or storage 412, and executed by the processing unit 408.
[0084] In case of any hardware implementations various networking devices 416 or external I/O devices 414 may be connected to the computing environment 402 to support the implementation through the networking unit and the I/O device unit.
[0085] The embodiments disclosed herein can be implemented through at least one software program running on at least one hardware device and performing network management functions to control the elements. The elements shown in the FIGS. 1 through 4 include blocks which can be at least one of a hardware device, or a combination of hardware device and software module.
[0086] The foregoing description of the specific embodiments will so fully reveal the general nature of the embodiments herein that others can, by applying current knowledge, readily modify and/or adapt for various applications such specific embodiments without departing from the generic concept, and, therefore, such adaptations and modifications should and are intended to be comprehended within the meaning and range of equivalents of the disclosed embodiments. It is to be understood that the phraseology or terminology employed herein is for the purpose of description and not of limitation. Therefore, while the embodiments herein have been described in terms of preferred embodiments, those skilled in the art will recognize that the embodiments herein can be practiced with modification within the spirit and scope of the embodiments as described herein.