Time Warp Activation Signal Provider, Audio Signal Encoder, Method for Providing
a Time Warp Activation Signal, Method for encoding an Audio Signal and Computer
Programs
Specification
The present invention is related to audio encoding and decoding and specifically for
encoding/decoding of audio signal having a harmonic or speech content, which can be
subjected to a time warp processing.
In the following, a brief introduction will be given into the field of time warped audio
encoding, concepts of which can be applied in conjunction with some of the embodiments
of the invention.
In the recent years, techniques have been developed to transform an audio signal into a
frequency domain representation, and to efficiently encode this frequency domain
representation, for example taking into account perceptual masking thresholds. This
concept of audio signal encoding is particularly efficient if the block length, for which a set
of encoded spectral coefficients are transmitted, are long, and if only a comparatively small
number of spectral coefficients are well above the global masking threshold while a large
number of spectral coefficients are nearby or below the global masking threshold and can
thus be neglected (or coded with minimum code length).
For example, cosine-based or sine-based modulated lapped transforms are often used in
applications for source coding due to their energy compaction properties. That is, for
harmonic tones with constant fundamental frequencies (pitch), they concentrate the signal
energy to a low number of spectral components (sub-bands), which leads to an efficient
signal representation.
Generally, the (fundamental) pitch of a signal shall be understood to be the lowest
dominant frequency distinguishable from the spectrum of the signal. In the common
speech model, the pitch is the frequency of the excitation signal modulated by the human
throat. If only one single fundamental frequency would be present, the spectrum would be
extremely simple, comprising the fundamental frequency and the overtones only. Such a
spectrum could be encoded highly efficiently. For signals with varying pitch, however, the
energy corresponding to each harmonic component is spread over several transform
coefficients, thus leading to a reduction of coding efficiency.

In order to overcome this reduction of coding efficiency, the audio signal to be encoded is
effectively resampled on a non-uniform temporal grid. In the subsequent processing, the
sample positions obtained by the non-uniform resampling are processed as if they would
represent values on a uniform temporal grid. This operation is commonly denoted by the
phrase 'time warping'. The sample times may be advantageously chosen in dependence on
the temporal variation of the pitch, such that a pitch variation in the time warped version of
the audio signal is smaller than a pitch variation in the original version of the audio signal
(before time warping). This pitch variation may also be denoted with the phrase "time
warp contour". After time warping of the audio signal, the time warped version of the
audio signal is converted into the frequency domain. The pitch-dependent time warping
has the effect that the frequency domain representation of the time warped audio signal
typically exhibits an energy compaction into a much smaller number of spectral
components than a frequency domain representation of the original (non time warped)
audio signal.
At the decoder side, the frequency-domain representation of the time warped audio signal
is converted back to the time domain, such that a time-domain representation of the time
warped audio signal is available at the decoder side. However, in the time-domain
representation of the decoder-sided reconstructed time warped audio signal, the original
pitch variations of the encoder-sided input audio signal are not included. Accordingly, yet
another time warping by resampling of the decoder-sided reconstructed time domain
representation of the time warped audio signal is applied. In order to obtain a good
reconstruction of the encoder-sided input audio signal at the decoder, it is desirable that the
decoder-sided time warping is at least approximately the inverse operation with respect to
the encoder-sided time warping. In order to obtain an appropriate time warping, it is
desirable to have an information available at the decoder which allows for an adjustment of
the decoder-sided time warping.
As it is typically required to transfer such an information from the audio signal encoder to
the audio signal decoder, it is desirable to keep a bit rate required for this transmission
small while still allowing for a reliable reconstruction of the required time warp
information at the decoder side.
In view of the above discussion, there is a desire to create a concept which allows for a
bitrate efficient application of the time warp concept in an audio encoder.

It is an object of the invention to create concepts for improving the hearing impression
provided by an encoded audio signal on the basis of information available in a time
warping audio signal encoder or a time warping audio signal decoder.
This object is achieved by a time warp activation signal provider for providing a time warp
activation signal on the basis of a representation of an audio signal in accordance with
claim 1, an audio signal encoder for encoding an input audio signal in accordance with
claim 12, a method for providing a time warp activation signal in accordance with claim
14, a method for providing an encoded representation of an input audio signal in
accordance with claim 15, or a computer program in accordance with claim 16.
It is a further object of the present invention to provide an improved audio
encoding/decoding scheme, which provides a higher quality or a lower bitrate.
This object is achieved by an audio encoder in accordance with claim 17, 26, 32, 37, an
audio decoder in accordance with claim 20, a method of audio encoding in accordance
with claim 23, claim 30, claim 35 or claim 37, a method of decoding in accordance with
claim 24, or a computer program in accordance with claim 25, 31, 36, or 43.
Embodiments according to the invention are related to methods for a time warped MDCT
transform coder. Some embodiments are related to encoder-only tools. However, other
embodiments are also related to decoder tools.
An embodiment of the invention creates a time warp activation signal provider for
providing a time warp activation signal on the basis of a representation of an audio signal.
The time warp activation signal provider comprises an energy compaction information
provider configured to provide an energy compaction information describing a compaction
of energy in a time warp transformed spectrum representation of the audio signal. The time
warp activation signal provider also comprises a comparator configured to compare the
energy compaction information with a reference value, and to provide the time warp
activation signal in dependence on a result of the comparison.
This embodiment is based on the finding that the usage of a time warp functionality in an
audio signal encoder typically brings along an improvement, in the sense of a reduction of
the bitrate of the encoded audio signal, if the time warp transformed spectrum
representation of the audio signal comprises a sufficiently compact energy distribution in
that the energy is concentrated in one or more spectral regions (or spectral lines). This is
due to the fact that a successful time warping brings along the effect of decreasing the

bitrate by transforming a smeared spectrum, for example of an audio frame, into the
spectrum having one or more discernable peaks, and consequently having a higher energy
compaction than the spectrum of the original (non-time-warped) audio signal.
Regarding this issue, it should be understood that an audio signal frame, during which the
pitch of the audio signal varies significantly, comprises a smeared spectrum. The time
varying pitch of the audio signal has the effect that a time-domain to a frequency-domain
transformation performed over the audio signal frame results in a smeared distribution of
the signal energy over the frequency, particularly in the higher frequency region.
Accordingly, a spectrum representation of such an original (non-time warped) audio signal
comprises a low energy compaction and typically does not exhibit spectral peaks in a
higher frequency portion of the spectrum, or only exhibits relatively small spectral peaks in
the higher frequency portion of the spectrum. In contrast, if time warping is successful (in
terms of providing an improvement of the encoding efficiency) the time warping of the
original audio signal yields a time warped audio signal having a spectrum with relatively
higher and clear peaks (particularly in the higher frequency portion of the spectrum). This
is due to the fact that an audio signal having a time varying pitch is transformed into a time
warped audio signal having a smaller pitch variation or even an approximately constant
pitch. Consequently, the spectrum representation of the time warped audio signal (which
can be considered as a time warp transformed spectrum representation of the audio signal)
comprises one or more clear spectral peaks. In other words, the smearing of the spectrum
of the original audio signal (having temporally variable pitch) is reduced by a successful
time warp operation, such that the time warp transformed spectrum representation of the
audio signal comprises higher energy compaction than the spectrum of the original audio
signal. Nevertheless, time warping is not always successful in improving the coding
efficiency. For example, time warping does not improve the coding efficiency if the input
audio signal comprises large noise components, or if the extracted time warp contour is
inaccurate.
In view of this situation, the energy compaction information provided by the energy
compaction information provider is a valuable indicator for deciding whether the time
warp is successful in terms of reducing the bitrate.
An embodiment of the invention creates a time warp activation signal provider for
providing a time warp activation signal on the basis of a representation of an audio signal.
The time warp activation provider comprises two time warp representation providers
configured to provide two time warp representations of the same audio signal using
different time warp contour information. Thus, the time warp representation providers may

be configured (structurally and/or functionally) in the same way and use the same audio
signal but different time warp contour information. The time warp activation signal
provider also comprises two energy compaction information providers configured to
provide a first energy compaction information on the basis of the first time warp
representation and to provide a second energy compaction information on the basis of the
second time warp representation. The energy compaction information providers may be
configured in the same way but to use the different time warp representations. Furthermore
the time warp activation signal provider comprises a comparator to compare the two
different energy compaction information and to provide the time warp activation signal in
dependence on a result of the comparison.
In a preferred embodiment, the energy compaction information provider is configured to
provide a measure of spectral flatness describing the time warp transformed spectrum
representation of the audio signal as the energy compaction information. It has been found
that time warp is successful, in terms of reducing a bitrate, if it transforms a spectrum of an
input audio signal into a less flat time warp spectrum representing a time warped version of
the input audio signal. Accordingly, the measure of spectral flatness can be used to decide,
without performing a full spectral encoding process, whether the time warp should be
activated or deactivated.
In a preferred embodiment, the energy compaction information provider is configured to
compute a quotient of a geometric mean of the time warp transformed power spectrum and
an arithmetic mean of the time warp transformed power spectrum, to obtain the measure of
the spectral flatness. It has been found that this quotient is a measure of spectral flatness
which is well adapted to describe the possible bitrate savings obtainable by a time warping.
In another preferred embodiment, the energy compaction information provider is
configured to emphasize a higher-frequency portion of the time warp transformed
spectrum representation when compared to a lower-frequency portion of the time warp
transformed spectrum representation, to obtain the energy compaction information. This
concept is based on the finding that the time warp typically has a much larger impact on
the higher frequency range than on the lower frequency range. Accordingly, a dominant
assessment of the higher frequency range is appropriate in order to determine the
effectiveness of the time warp using a spectral flatness measure. In addition, typical audio
signals exhibit a harmonic content (comprising harmonics of a fundamental frequency)
which decays in intensity with increasing frequency. An emphasis of a higher frequency
portion of the time warp transformed spectrum representation when compared to a lower

frequency portion of the time warp transformed spectrum representation also helps to
compensate for this typical decay of the spectral lines with increasing frequency. To
summarize, an emphasized consideration of the higher frequency portion of the spectrum
brings along an increased reliability of the energy compaction information and therefore
allows for a more reliable provision of the time warped activation signal.
In another preferred embodiment, the energy compaction information provider is
configured to provide a plurality of band-wise measures of spectral flatness, and to
compute an average of the plurality of band-wise measures of sp'ectral flatness, to obtain
the energy compaction information. It has been found that the consideration of band-wise
spectral flatness measures brings along a particularly reliable information as to whether the
time warp is effective to reduce the bitrate of an encoded audio signal. Firstly, the
encoding of the time warp transformed spectrum representation is typically performed in a
band-wise manner, such that a combination of the band-wise measures of spectral flatness
is well adapted to the encoding and therefore represents an obtainable improvement of the
bitrate with good accuracy. Further, a band-wise computation of measures of spectral
flatness substantially eliminates the dependency of the energy compaction information
from a distribution of the harmonics. For example, even if a higher frequency band
comprises a relatively small energy (smaller than the energies of lower frequency bands),
the higher frequency band may still be perceptually relevant. However, the positive impact
of a time warp (in the sense of a reduction of the smearing of the spectral lines) on this
higher frequency band would be considered as small, simply because of the small energy
of the higher frequency band, if the spectral flatness measure would not be computed in a
band-wise manner. In contrast, by applying the band-wise calculation, a positive impact of
the time warp can be taken into consideration with an appropriate weight, because the
band-wise spectral flatness measures are independent from the absolute energies in the
respective frequency bands.
In another preferred embodiment, the time warp activation signal provider comprises a
reference value calculator configured to compute a measure of spectral flatness describing
an non-time-warped spectrum representation of the audio signal, to obtain the reference
value. Accordingly, the time warp activation signal can be provided on the basis of a
comparison of the spectral flatness of a non-time-warped (or "unwarped") version of the
input audio signal and a spectral flatness of a time warped version of the input audio
signal.
In another preferred embodiment, the energy compaction information provider is
configured to provide a measure of perceptual entropy describing the time warp

transformed spectrum representation of the audio signal as the energy compaction
information. This concept is based on the finding that the perceptual entropy of the time
warp transformed spectrum representation is a good estimate of a number of bits (or a
bitrate) required to encode the time warp transformed spectrum. Accordingly, the measure
of perceptual entropy of the time warp transformed spectrum representation is a good
measure of whether a reduction of the bitrate can be expected by the time warping, even in
view of the fact that an additional time warp information must be encoded if the time warp
is used.
In another preferred embodiment, the energy compaction information provider is
configured to provide an autocorrelation measure describing an autocorrelation of a time
warped representation of the audio signal as the energy compaction information. This
concept is based on the finding that the efficiency of the time warp (in terms of reducing
the bitrate) can be measured (or at least estimated) on the basis of a time warped (or a non-
uniformly resampled) time domain signal. It has been found that time warping is efficient
if the time warped time domain signal comprises a relatively high degree of periodicity,
which is reflected by the autocorrelation measure. In contrast, if the time warped time
domain signal does not comprise a significant periodicity, it can be concluded that the time
warping is not efficient.
This finding is based on the fact that an efficient time warp transforms a portion of a
sinusoidal signal of a varying frequency (which does not comprise a periodicity) into a
portion of a sinusoidal signal of approximately constant frequency (which comprises a high
degree of periodicity). In contrast, if the time warping is not capable of providing a time
domain signal having a high degree of periodicity, it can be expected that the time warping
also does not provide a significant bitrate saving, which would justify its application.
In a preferred embodiment, the energy compaction information provider is configured to
determine a sum of absolute values of a normalized autocorrelation function (over a
plurality of lag values) of the time warped representation of the audio signal, to obtain the
energy compaction information. It has been found that a computationally complex
determination of the autocorrelation peaks is not required to estimate the efficiency of the
time warping. Rather, it has been found that a summing evaluation of the autocorrelation
over a (wide) range of autocorrelation lag values also brings along very reliable results.
This is due to the fact that the time warp actually transforms a plurality of signal
components (e.g. a fundamental frequency and harmonics thereof) of varying frequency
into periodic signal components. Accordingly, the autocorrelation of such a time warped
signal exhibits peaks at a plurality of autocorrelation lag values. Thus, a sum-formation is a

computationally efficient way of extracting the energy compaction information from the
autocorrelation.
In another preferred embodiment, the time warp activation signal provider comprises a
reference value calculator configured to compute the reference value on the basis of an
non-time-warped spectral representation of the audio signal or on the basis of an non-time-
warped time domain representation of the audio signal. In this case, the comparator is
typically configured to form a ratio value using the energy compaction information
describing a compaction of energy in a time warp transformed spectrum of the audio signal
and the reference value. The comparator is also configured to compare the ratio value with
one or more threshold values to obtain the time warp activation signal. It has been found
that the ratio between an energy compaction information in the non-time-warped case and
the energy compaction information in the time warped case allows for a computationally
efficient but still sufficiently reliable generation of the time warp activation signal.
Another preferred embodiment of the invention creates an audio signal encoder for
encoding an input audio signal, to obtain an encoded representation of the input audio
signal. The audio signal encoder comprises a time warp transformer configured to provide
a time warp transformed spectrum representation on the basis of the input audio signal.
The audio signal encoder also comprises a time warp activation signal provider, as
described above. The time warp activation signal provider is configured to receive the
input audio signal and to provide the energy compaction information such that the energy
compaction information describes a compaction of energy in the time warp transformed
spectrum representation of the input audio signal. The audio signal encoder further
comprises a controller configured to selectively provide, in dependence on the time warp
activation signal, a found non-constant (varying) time warp contour portion or time
warping information, or a standard constant (non-varying) time warp contour portion or
time warping information to the time warp transformer. In this way, it is possible to
selectively accept or reject a found non-constant time warp contour portion in the
derivation of the encoded audio signal representation from the input audio signal.
This concept is based on the finding that it is not always efficient to introduce a time warp
information into an encoded representation of the input audio signal, because a remarkable
number of bits is required for encoding the time warp information. Further, it has been
found that the energy compaction information, which is computed by the time warp
activation signal provider, is a computationally efficient measure to decide whether it is
advantageous to provide the time warp transformer with the found varying (non-constant)
time warp contour portion or a standard (non-varying, constant) time warp contour. It has

to be noted that when the time warp transformer comprises an overlapping transform, a
found time warp contour portion may be used in the computation of two or more
subsequent transform blocks. In particular, it has been found that it is not necessary to fully
encode both the version of the time warp transformed spectral representation of the input
audio signal using the newly found varying time warp contour portion and the version of
the time warp transformed spectral representation of the input audio signal using a standard
(non-varying) time warp contour portion in order to be able to make a decision whether the
time warping allows for a saving in bitrate or not. Rather, it has been found that an
evaluation of the energy compaction of the time warp transformed spectral representation
of the input audio signal forms a reliable basis of the decision. Accordingly, a required
bitrate can be kept small.
In a further preferred embodiment, the audio signal encoder comprises an output interface
configured to selectively include, in dependence on the time warp activation signal, a time
warp contour information representing a found varying time warp contour into the encoded
representation of the audio signal Thus, a high efficiency of the audio signal encoding can
be obtained, irrespective of whether the input signal is well suited for time warping or not.
A further embodiment according to the invention creates a method for providing a time
warp activation signal on the basis of an audio signal. The method fulfills the functionality
of the time warp activation signal provider and can be supplemented by any of the features
and functionalities described here with respect to the time warp activation signal provider.
Another embodiment according to the invention creates a method for encoding an input
audio signal, to obtain an encoded representation of the input audio signal. This method
can be supplemented by any of the features and functionalities described herein with
respect to the audio signal encoder.
Another embodiment according to the invention creates a computer program for
performing the methods mentioned herein.
In accordance with a first aspect of the present invention, an audio signal analysis, whether
an audio signal has a harmonic characteristic or a speech characteristic is advantageously
used for controlling a noise filling processing on the encoder side and/or on the decoder
side. The audio signal analysis is easily obtainable in a system, in which a time warp
functionality is used, since this time warp functionality typically comprises a pitch tracker
and/or a signal classifier for distinguishing between speech on the one hand and music on
the other hand and/or for distinguishing between voiced speech and unvoiced speech.

Since this information is available in such a context without any further costs, the
information available is advantageously used for controlling the noise filling feature so
that, especially for speech signals, a noise filling in between harmonic lines is reduced or,
for speech signals in particular, even eliminated. Even in situations, where a strong
harmonic content is obtained, but a speech is not directly detected by a speech detector, a
reduction of noise filling nevertheless will result in a higher perceived quality. Although
this feature is particularly useful in a system, in which the harmonic/speech analysis is
performed anyway, and this information is, therefore, available without any additional
costs, the control of the noise filling scheme based on a signal analysis, whether the signal
has a harmonic or speech characteristic or not is additionally useful, even when a specific
signal analyzer has to be inserted into the system, since the quality is enhanced without
bitrate increase or, stated alternatively, the bitrate is decreased without having a loss in
quality, since the bits required for encoding the noise filling level are reduced when the
noise filling level itself, which can be transmitted from an encoder to a decoder, is reduced.
In a further aspect of the present invention, the signal analysis result, i.e., whether the
signal is a harmonic signal or a speech signal is used for controlling the window function
processing of an audio encoder. It has been found that in a situation, in which a speech
signal or a harmonic signal starts, the possibility is high that a straightforward encoder will
switch from long windows to short windows. These short windows, however, have a
correspondingly reduced frequency resolution which, on the other hand, would decrease
the coding gain for strongly harmonic signals and therefore increase the number of bits
needed to code such signal portion. In view of that, the present invention defined in this
aspect uses windows longer than a short window when a speech or harmonic signal onset
is detected. Alternatively, windows are selected with a length roughly similar to the long
windows, but with a shorter overlap in order to effectively reduce pre-echoes. Generally,
the signal characteristic, whether the time frame of an audio signal has a harmonic or a
speech characteristic is used for selecting a window function for this time frame.
In accordance with a further aspect of the present invention, the TNS (temporal noise
shaping) tool is controlled based on whether the underlying signal is based on a time
warping operation or is in a linear domain. Typically, a signal which has been processed by
a time warping operation will have a strong harmonic content. Otherwise, a pitch tracker
associated with a time warping stage would not have output a valid pitch contour and, in
the absence of such a valid pitch contour, a time warping functionality would have been
deactivated for this time frame of the audio signal. However, harmonic signals will,
normally, not be suitable for being subjected to the TNS processing. The TNS processing
is particularly useful and induces a significant gain in bitrate/quality, when the signal

processed by the TNS stage has a quite flat spectrum. When, however, the appearance of
the signal is tonal, i.e., non-flat, as is the case for spectra having a harmonic content or
voiced content, the gain in quality/bitrate provided by the TNS tool will be reduced.
Therefore, without the inventive modification of the TNS tool, time-warped portions
typically would not be TNS processed, but would be processed without a TNS filtering. On
the other hand, the noise shaping feature of TNS nevertheless provides an improved quality
specifically in situations, where the signal is varying in amplitude/power. In cases, where
an onset of an harmonic signal or speech signal is present, and where the block switching
feature is implemented so that, instead of this onset, long windows or at least windows
longer than short windows are maintained, the activation of the temporal noise shaping
feature for this frame will result in a concentration of the noise around the speech onset
which effectively reduces pre-echoes, which might occur before the onset of the speech
due to a quantization of the frame occurring in a subsequent encoder processing.
In accordance with a further aspect of the present invention, a variable number of lines is
processed by a quantizer/entropy encoder within an audio encoding apparatus, in order to
account for the variable bandwidth, which is introduced from frame to frame due to
performing a time warping operation with a variable time warping characteristic/warping
contour. When the time warping operation results in the situation that the time of the frame
(in linear terms) included in a time warped frame is increased, the bandwidth of a single
frequency line is decreased, and, for a constant overall bandwidth, the number of frequency
lines to processed is to be increased regarding a non-time warp situation. When, on the
other hand, the time warping operation results in the fact that the actual time of the audio
signal in the time warped domain is decreased with respect to the block length of the audio
signal in the linear domain, the frequency bandwidth of a single frequency line is increased
and, therefore, the number of lines processed by a source encoder has to be decreased with
respect to a non-time-warping situation in order to have a reduced bandwidth variation or,
optimally, no bandwidth variation.
Preferred embodiments are subsequently described with respect to the accompanying
drawings, in which:
Fig. 1 shows a block schematic diagram of a time warp activation signal provider,
according to an embodiment of the invention;
Fig. 2a shows a block schematic diagram of an audio signal encoder, according to

Fig. 2b shows another a block schematic diagram of a time warp activation signal
provider according to an embodiment of the invention;
Fig. 3 a shows a graphical representation of a spectrum of an non-time-warped
version of an audio signal;
Fig. 3b shows a graphical representation of a spectrum of a time warped version of
the audio signal;
Fig. 3 c shows a graphical representation of an individual calculation of spectral
flatness measures for different frequency bands;
Fig. 3d shows a graphical representation of a calculation of a spectral flatness
measure considering only the higher frequency portion of the spectrum;
Fig. 3e shows a graphical representation of a calculation of a spectral flatness
measure using a spectrum representation in which a higher frequency
portion is emphasized over a lower frequency portion;
Fig. 3f shows a block schematic diagram of an energy compaction information
provider, according to another embodiment of the invention;
Fig. 3g shows a graphical representation of an audio signal having a temporally
variable pitch in the time domain;
Fig. 3h shows a graphical representation of a time warped (non-uniformly
resampled) version of the audio signal of Fig. 3g;
Fig. 3i shows a graphical representation of an autocorrelation function of the audio
signal according to Fig. 3g;
Fig. 3j shows a graphical representation of an autocorrelation function of the audio
signal according to Fig. 3h;
Fig. 3k shows a block schematic diagram of an energy compaction information
provider, according to another embodiment of the invention;

Fig. 4a shows a flowchart of a method for providing a time warp activation signal
on the basis of an audio signal;
Fig. 4b shows a flowchart of a method for encoding an input audio signal to obtain
an encoded representation of the input audio signal, according to an
embodiment of the invention;
Fig. 5 a illustrates a preferred embodiment of an audio encoder having inventive
aspects;
Fig. 5b illustrates a preferred embodiment of an audio decoder having inventive
aspects;
Fig. 6a illustrates a preferred embodiment of the noise filling aspect of the present
invention;
Fig. 6b illustrates a table defining the control operation performed by the noise
filling level manipulator;
Fig. 7a illustrates a preferred embodiment for performing a time warp-based block
switching in accordance with the present invention;
Fig. 7b illustrates an alternative embodiment for influencing the window function;
Fig. 7c illustrates a further alternative embodiment for illustrating the window
function based on time warp information;
Fig. 7d illustrates a window sequence of a normal AAC behavior at a voiced onset;
Fig. 7e illustrates alternative window sequences obtained in accordance with a
preferred embodiment of the present invention;
Fig. 8a illustrates the preferred embodiment of a time warp-based control of the
TNS (temporal noise shaping) tool;
Fig. 8b illustrates a table defining control procedures performed in the threshold
control signal generator in Fig. 8a;

Fig. 9a-9e illustrate different time warping characteristics and the corresponding
influence on the bandwidth of the audio signal occurring subsequent to a
decoder-side time dewarping operation;
Fig. 10a illustrates a preferred embodiment of a controller for controlling the number
of lines within an encoding processor;
Fig. 10b illustrates a dependence between the number of lines to be discarded/added
for a sampling rate;
Fig. 11 illustrates a comparison between a linear time scale and a warped time
scale;
Fig. 12a illustrates an implementation in the context of bandwidth extension; and
Fig. 12b illustrates a table showing the dependence between the local sampling
rate in the time warped domain and the control of spectral coefficients.
Fig. 1 shows a block schematic diagram of the time warp activation signal provider,
according to an embodiment of the invention. The time warp activation signal provider 100
is configured to receive a representation 110 of an audio signal and to provide, on the basis
thereof, a time warp activation signal 112. The time warp activation signal provider 100
comprises an energy compaction information provider 120, which is configured to provide
an energy compaction information 122, describing a compaction of energy in a time warp
transformed spectrum representation of the audio signal. The time warp activation signal
provider 100 further comprises a comparator 130 configured to compare the energy
compaction information 122 with a reference value 132, and to provide the time warp
activation signal 112 in dependence on the result of the comparison.
As discussed above, it has been found that the energy compaction information is a valuable
information which allows for a computationally efficient estimation whether a time warp
brings along a bit saving or not. It has been found that the presence of a bit saving is
closely correlated with the question whether the time warp results in a compaction of
energy or not.
Fig. 2a shows a block schematic diagram of an audio signal encoder 200, according to an
embodiment of the invention. The audio signal encoder 200 is configured to receive an
input audio signal 210 (also designated to a(t)) and to provide, on the basis thereof, an

encoded representation 212 of the input audio signal 210. The audio signal encoder 200
comprises a time warp transformer 220, which is configured to receive the input audio
signal 210 (which may be represented in a time domain) and to provide, on the basis
thereof, a time warp transformed spectral representation 222 of the input audio signal 210.
The audio signal encoder 200 further comprises a time warp analyzer 284, which is
configured to analyze the input audio signal 210 and to provide, on the basis thereof, a time
warp contour information (e.g. absolute or relative time warp contour information) 286.
The audio signal encoder 200 further comprises a switching mechanism, for example in the
form of a controlled switch 240, to decide whether the found time warp contour
information 286 or a standard time warp contour information 288 is used for further
processing. Thus, the switching mechanism 240 is configured to selectively provide, in
dependence on a time warp activation information, either the found time warp contour
information 286 or a standard time warp contour information 288 as new time warp
contour information 242, for a further processing, for example to the time warp
transformer 220. It should be noted, that the time warp transformer 220 may for example
use the new time warp contour information 242 (for example a new time warp contour
portion) and, in addition, a previously obtained time warp information (for example one or
more previously obtained time warp contour portions) for the time warping of an audio
frame. The optional spectrum post processing may for example comprise a temporal noise
shaping and/or a noise filling analysis. The audio signal encoder 200 also comprises a
quantizer/encoder 260, which is configured to receive the spectral representation 222
(optionally processed by the spectrum post processing 250) and to quantize and encode the
transformed spectral representation 222. For this purpose, the quantizer/encoder 260 may
be coupled with a perceptual model 270 and receive a perceptual relevance information
272 from the perceptual model 270, to consider a perceptual masking and to adjust
quantization accuracies in different frequency bins in accordance with the human
perception. The audio signal encoder 200 further comprises an output interface 280 which
is configured to provide the encoded representation 212 of the audio signal on the basis of
the quantized and encoded spectral representation 262 provided by the quantizer/encoder
260.
The audio signal encoder 200 further comprises a time warp activation signal provider 230,
which is configured to provide a time warp activation signal 232. The time warp activation
signal 232 may, for example, be used to control the switching mechanism 240, to decide
whether the newly found time warp contour information 286 or a standard time warp
contour information 288 is used in further processing steps (for example by the time warp
transformer 220). Further, the time warp activation information 232 may be used in a

switch 280 to decide whether the selected new time warp contour information 242
(selected from newly found time warp contour information 286 and the standard time warp
contour information) is included into the encoded representation 212 of the input audio
signal 210. Typically, time warp contour information is only included into the encoded
representation 212 of the audio signal if the selected time warp contour information
describes a non-constant (varying) time warp contour. Also, time warp activation
information 232 may itself be included into the encoded representation 212, for example in
form of a one-bit flag indicating an activation or a deactivation of the time warp.
In order to facilitate the understanding, it should be noted that the time warp transformer
220 typically comprises an analysis windower 220a, a resampler or "time warper" 220b
and a spectral domain transformer (or time/frequency converter) 220c. Depending on the
implementation, however, the time warper 220b can be placed - in a signal processing
direction - before the analysis windower 220a. However, time warping and time domain
to spectral domain transformation may be combined in a single unit in some embodiments.
In the following, details regarding the operation of the time warp activation signal provider
230 will be described. It should be noted that the time warp activation signal provider 230
may be equivalent to the time warp activation signal provider 100.
The time warp activation signal provider 230 is preferably configured to receive the time
time domain audio signal representation 210 (also designated with a(t)), the newly found
time warp contour information 286, and the standard time warp contour information 288.
The time warp activation signal provider 230 is also configured to obtain, using the time
domain audio signal 210, the newly found time warp contour information 286 and the
standard time warp contour information 288, an energy compaction information describing
a compaction of energy due to the newly found time warp contour information 286, and to
provide the time warp activation signal 232 on the basis of this energy compaction
information.
Fig. 2b shows a block schematic diagram of a time warp activation signal provider 234,
according to an embodiment of the invention. The time warp activation signal provider 234
may take the role of the time warp activation signal provider 230 in some embodiments.
The time warp activation signal provider 234 is configured to receive an input audio signal
210, and two time warp contour information 286 and 288, and provide, on the basis
thereof, a time warp activation signal 234p. The time warp activation signal 234p may take
the role of the time warp activation signal 232. The time warp activation signal provider
comprises two identical time warp representation providers 234a, 234g, which are

configured to receive the input audio signal 210 and the time warp contour information 286
and 288 respectively and to provide, on the basis thereof, two time warped representations
234e and 234k, respectively. The time warp activation signal provider 234 further
comprises two identical energy compaction information providers 234f and 2341, which are
configured to receive the time warped representations 234e and 234k, respectively, and, on
the basis thereof, provide the energy compaction information 234m and 234n, respectively.
The time warp activation signal provider further comprises a comparator 234o, configured
to receive the energy compaction information 234m and 234n, and, on the basis thereof
provide the time warp activation signal 234p.
In order to facilitate the understanding, it should be noted that the time warp representation
providers 234a and 234g typically comprises (optional) identical analysis windowers 234b
and 234h, identical resamplers or time warpers 234c and 234i, and (optional) identical
spectral domain transformers 234d and 234j.
In the following, different concepts for obtaining the energy compaction information will
be discussed. Beforehand, an introduction will be given explaining the effect of time
warping on a typical audio signal.
In the following, the effect of time warping on an audio signal will be described taking
reference to Figs. 3a and 3b. Fig. 3a shows a graphical representation of a spectrum of an
audio signal. An abscissa 301 describes a frequency and an ordinate 302 describes an
intensity of the audio signal. A curve 303 describes an intensity of the non-time-warped
audio signal as a function of the frequency f.
Fig. 3b shows a graphical representation of a spectrum of a time warped version of the
audio signal represented in Fig. 3a. Again, an abscissa 306 describes a frequency and an
ordinate 307 describes the intensity of the warped version of the audio signal. A curve 308
describes the intensity of the time warped version of the audio signal over frequency. As
can be seen from a comparison of the graphical representation of Figs. 3a and 3b, the non-
time-warped ("unwarped") version of the audio signal comprises a smeared spectrum,
particularly in a higher frequency region. In contrast, the time warped version of the input
audio signal comprises a spectrum having clearly distinguishable spectral peaks, even in
the higher frequency region. In addition, a moderate sharpening of the spectral peaks can
even be observed in the lower spectral region of the time warped version of the input audio
signal.

It should be noted that the spectrum of the time warped version of the input audio signal,
which is shown in Fig. 3b, can be quantized and encoded, for example by the
quantizer/encoder 260, with a lower bitrate than the spectrum of the unwarped input audio
signal shown in Fig. 3 a. This is due to the fact that a smeared spectrum typically comprises
a large number of perceptually relevant spectral coefficients (i.e. a comparatively small
number of spectral coefficients quantized to zero or quantized to small values), while a
"less flat" spectrum as shown in Fig. 3 typically comprises a larger number of spectral
coefficients quantized to zero or quantized to small values. Spectral coefficients quantized
to zero or quantized to small values can be encoded with less bits than spectral coefficients
quantized to higher values, such that the spectrum of Fig. 3b can be encoded using less bits
than the spectrum of Fig. 3 a.
Nevertheless, it should also be noted that the usage of a time warp does not always result in
a significant improvement of the coding efficiency of the time warped signal. Accordingly,
in some cases the price, in terms of bitrate, required for the encoding of the time warp
information (e.g. time warp contour) may exceed the savings, in terms of bitrate, for
encoding the time warp transformed spectrum (when compared to encoding the non time
warp transformed spectrum). In this case, it is preferable to provide the encoded
representation of the audio signal using a standard (non-varying) time warp contour to
control the time warp transform. Consequently, the transmission of any time warp
information (i.e. time warp contour information) can be omitted (except for a flag
indicating the deactivation of the time warping), thereby keeping the bitrate low.
In the following, different concepts for a reliable and computationally efficient calculation
of a time warp activation signal 112, 232, 234p will be described taking reference to Figs.
3c-3k. However, before that, the background of the inventive concept will be briefly
summarized.
The basic assumption is that applying the time warping on a harmonic signal with a
varying pitch makes the pitch constant, and that making the pitch constant improves the
coding of spectra obtained by a following time-frequency transform, because instead of the
smearing of the different harmonics over several spectral bins (see Figs. 3a) only a limited
number of significant lines remain (see Fig. 3b). However, even when a pitch variation is
detected, the improvement in coding gain (i.e. the amount of bits saved) may be negligible
(e.g. if one has strong noise underlying the harmonic signal, or if the variation is so small
that the smearing of higher harmonics is no problem), or may be less than the amount of
bits needed to transfer the time warp contour to the decoder, or may simply be wrong. In
these cases, it is preferable to reject the varying time warp contour (e.g. 286) produced by a

time warp contour encoder and instead use an efficient one-bit signaling, signaling a
standard (non-varying) time warp contour.
The scope of the present invention comprises the creation of a method to decide if an
obtained time warp contour portion provides enough coding gain (for example enough
coding gain to compensate for the overhead required for the encoding to the time warp
contour).
As stated above, the most important aspect of the time warping is the compaction of the
spectral energy to a fewer number of lines (see Figs. 3a and 3b). One look at this shows
that a compaction of energy also corresponds to a more "unflat" spectrum (see Figs. 3a and
3b), since the difference between peaks and valleys of the spectrum is increased. The
energy is concentrated at fewer lines with the lines in between those having less energy
than before.
Figs. 3a and 3b show a schematic example with an unwarped spectrum of a frame with
strong harmonics and pitch variation (Fig. 3a) and the spectrum of the time warped version
of the same frame (Fig. 3b).
In view of this situation, it has been found that it is advantageous to use the spectral
flatness measure as a possible measure for the efficiency of the time warping.
The spectral flatness may be calculated, for example, by dividing the geometric mean of
the power spectrum by the arithmetic mean of the power spectrum. For example, the
spectral flatness (also designated briefly as "flatness") can be computed according to the
following equation:

In the above, x(n) represents the magnitude of a bin number n. In addition, in the above, N
represents a total number of spectral bins considered for the calculation of the spectral
flatness measure.
In an embodiment of the invention, the above-mentioned calculation of the "flatness",
which may serve as an energy compaction information, may be performed using the time

warp transformed spectrum representations 234e, 234k, such that the following
relationship may hold:

In this case, N may be equal to the number of spectral lines provided by the spectral
domain transformer 234d, 234j and | X | tw (n) is a time warped transformed spectrum
representation 234e, 234k.
Even though the spectral measure is a useful quantity for the provision of the time warp
activation signal, one drawback of the spectral flatness measure, like the signal-to-noise
ratio (SNR) measure, is that if applied to the whole spectrum, it emphasizes parts with
higher energy. Normally, harmonic spectra have a certain spectral tilt, meaning that most
of the energy is concentrated at the first few partial tones and then decreases with
increasing frequency, leading to an under-representation of the higher partials in the-
measure. This is not wanted in some embodiments, since it is desired to improve the
quality of these higher partials, because they get smeared the most (see Fig. 3a). In the
following, several optional concepts for the improvement of the relevance of the spectral
flatness measure will be discussed.
In an embodiment according to the invention, an approach similar to the so-called
"segmental SNR" measure is chosen, leading to a band-wise spectral flatness measure. A
calculation of the spectral flatness measure is performed (for example separately) within a
number of bands, and main (or mean) is taken. The different bands might have equal
bandwidth. However, preferably, the bandwidths may follow a perceptual scale, like
critical bands, or correspond, for example, to the scale factor bands of the so-called
"advanced audio coding", also known as AAC.
The above-mentioned concept will be briefly explained in the following, taking reference
to Fig. 3 c, which shows a graphical representation of an individual calculation of spectral
flatness measures for different frequency bands. As can be seen, the spectrum may be
divided into different frequency bands 311, 312, 313, which may have an equal bandwidth
or which may have different bandwidths. For example, a first spectral flatness measure
may be computed for the first frequency band 311, for example, using the equation for the
"flatness" given above. In this calculation, the frequency bins of the first frequency band
may be considered (running variable n may take the frequency bin indices of the frequency
bins of the first frequency band), and the width of the first frequency band 311 may be

considered (variable N may take the width in terms of frequency bins of the first frequency
band). Accordingly, a flatness measure for the first frequency band 311 is obtained.
Similarly, a flatness measure may be computed for the second frequency band 312, taking
into consideration the frequency bins of the second frequency bands 312 and also the width
of the second frequency band. Further, flatness measures of additional frequency bands,
like the third frequency band 313, may be computed in the same way.
Subsequently, an average of the flatness measures for different frequency bands 311, 312,
313 may be computed, and the average may serve as the energy compaction information.
Another approach (for the improvement of the derivation of the time warp activation
signal) is to apply the spectral flatness measure only above a certain frequency. Such an
approach is illustrated in Fig. 3b. As can be seen, only frequency bins in an upper
frequency portion 316 of the spectra are considered for a calculation of the spectral flatness
measure. A lower frequency portion of the spectrum is neglected for the calculation of the
spectral flatness measure. The higher frequency portion 316 may be considered frequency-
band-wise for the calculation of the spectral flatness measure. Alternatively, the entire
higher frequency portion 316 may be considered in its entirety for the calculation of the
spectral flatness measure.
To summarize the above, it can be stated that the decrease in the spectral flatness (caused
by the application of the time warp) may be considered as a first measure for the efficiency
of the time warping.
For example, the time warp activation signal provider 100, 230, 234 (or the comparator
130, 234o thereof) may compare the spectral flatness measure of the time warp
transformed spectral representation 234e with a spectral flatness measure of the time warp
transformed spectral representation 234k using a standard time warp contour information,
and to decide on the basis of said comparison whether the time warp activation signal
should be active or inactive. For example, the time warp is activated by means of an
appropriate setting of the time warp activation signal if the time warping results in a
sufficient reduction of the spectral flatness measure when compared to a case without time
warping.
In addition to the above mentioned approaches, the upper frequency portion of the
spectrum can be emphasized (for example by an appropriate scaling) over the lower
frequency portion for the calculation of the spectral flatness measure. Fig. 3 c shows a
graphical representation of a time warp transformed spectrum in which a higher frequency

portion is emphasized over a lower frequency portion. Accordingly, an under-
representation of higher partials in the spectrum is compensated. Thus, the flatness
measure can be computed over the complete scaled spectrum in which higher frequency
bins are emphasized over lower frequency bins, as shown in Fig. 3e.
In terms of bit savings, a typical measure of coding efficiency would be the perceptual
entropy, which can be defined in a way so that it correlates very nicely with the actual
number of bits needed to encode a certain spectrum as described in 3GPP TS 26.403
V7.0.0: 3rd Generation Partnership Project; Technical Specification Group Services and
System Aspects; General audio codec audio processing functions; Enhanced aacPlus
general audio codec; Encoder specification AAC part: Section 5.6.1.1.3 Relation between
bit demand and perceptual entropy. As a result, the reduction of the perceptual entropy is
another measure for the efficiency of the time warping would be.
Fig. 3f shows an energy compaction information provider 325, which may take the place of
the energy compaction information provider 120, 234f, 2341, and which may be used in the
time warp activation signal providers 100, 290, 234. The energy compaction information
provider 325 is configured to receive a representation of the audio signal, for example, in
the form of a time-warp transformed spectrum representation 234e, 234k, also designated
with | X | tw- The energy compaction information provider 325 is also configured to
provide a perceptual entropy information 326, which may take the place of the energy
compaction information 122, 234m, 234n.
The energy compaction information provider 325 comprises a form factor calculator 327,
which is configured to receive the time warp transformed spectrum representation 234e,
234k and to provide, on the basis thereof, a form factor information 328, which may be
associated with a frequency band. The energy compaction information provider 325 also
comprises a frequency band energy calculator 329, which is configured to calculate a
frequency band energy information en(n) (330) on the basis of the time warped spectrum
representation 234e, 234k. The energy compaction information provider 325 also
comprises a number of lines estimator 331, which is configured to provide an estimated
number of lines information nl (332) for a frequency band having index n. In addition, the
energy compaction information provider 325 comprises a perceptual entropy calculator
333, which is configured to compute the perceptual entropy information 326 on the basis
of the frequency band energy information 330 and of the estimated number of lines
information 332. For example, the form factor calculator 327 may be configured to
compute the form factor according to


In the above equation, ffac(n) designates the form factor for the frequency band having a
frequency band index n. k designates a running variable, which runs over the spectral bin
indices of the scale factor band (or frequency band) n. X(k) designates a spectral value (for
example, an energy value or a magnitude value) of the spectral bin (or frequency bin)
having a spectral bin index (or a frequency bin index) k.
The number of lines estimator may be configured to estimate the number of nonzero lines,
designated with nl, according to the following equation:

In the above equation, en(n) designates an energy in the frequency band or scale factor
band having index n. kOffset(n+l)-kOffset(n) designates a width of the frequency band or
scale factor band of index n in terms of frequency bins.
Furthermore, the perceptual entropy calculator 332 may be configured to compute the
perceptual entropy information sfbPe according to the following equation:
In the above, the following relations may hold:

A total perceptual entropy pe may be computed as the sum of the perceptual entropies of
multiple frequency bands or scale factor bands.
As mentioned above, the perceptional entropy information 326 may be used as an energy
compaction information.

For further details regarding the computation of the perceptual entropy, reference is made
to section 5.6.1.1.3 of the International Standard "3GPP TS 26.403 V7.0.0(2006-06)".
In the following, a concept will be described for the computation of the energy compaction
information in the time domain.
Another look at the TW-MDCT (time warped modified discrete cosine transform) is the
basic idea to change the signal in a way to have a constant or nearly constant pitch within
one block. If a constant pitch is achieved, this means that the maxima of the
autocorrelation of one process block increase. Since it is not trivial to find corresponding
maxima in the autocorrelation for the time warped and non-time-warped case, the sum of
the absolute values for the normalized autocorrelation can be used as a measure for the
improvement. An increase in this sum corresponds to an increase in the energy
compaction.
This concept will be explained in more detail in the following, taking reference to Figs. 3g,
3h, 3i, 3j and 3k.
Fig. 3g shows a graphical representation of an non-time-warped signal in the time domain.
An abscissa 350 describes the time, and an ordinate 351 describes a level a(t) of the non-
time-warped time signal. A curve 352 describes the temporal evolution of the non-time-
warped time signal. It is assumed that the frequency of the non-time-warped time signal
described by the curve 352 increases over time, as can be seen in Fig. 3g.
Fig. 3h shows a graphical representation of a time warped version of the time signal of Fig.
3g. An abscissa 355 describes the warped time (for example, in a normalized form) and an
ordinate 356 describes the level of the time warped version a(tw) of the signal a(t). As can
be seen in Fig. 3h, the time warped version a(tw) of the non-time-warped time signal a(t)
comprises (at least approximately) a temporally constant frequency in the warped time
domain.
In other words, Fig. 3h illustrates the fact that a time signal of a temporally varying
frequency is transformed into a time signal of a temporally constant frequency by an
appropriate time warped operation, which may comprise a time-warping re-sampling.
Fig. 3i shows a graphical representation of an autocorrelation function of the unwarped
time signal a(t). An abscissa 360 describes an autocorrelation lag x, and an ordinate 361
describes a magnitude of the autocorrelation function. Marks 362 describe an evolution of

the autocorrelation function Ruw(ι) as a function of the autocorrelation lag T. AS can be
seen from Fig. 3i, the autocorrelation function Ruw of the unwarned time signal a(t)
comprises a peak for ι = 0 (reflecting the energy of the signal a(t)) and takes small values
fort ± 0.
Fig. 3j shows a graphical representation of the autocorrelation function Rtw of the time
warped time signal a(tw). As can be seen from Fig. 3j, the autocorrelation function Rtw
comprises a peak for ι = 0, and also comprises peaks for other values ι1,ι2, ι3 of the
autocorrelation lag ι. These additional peaks for ι1, ι2, ι3 are obtained by the effect of the
time warp to increase the periodicity of the time warped time signal a(tw). This periodicity
is reflected by the additional peaks of the autocorrelation function Rtw (ι) when compared
to the autocorrelation function Ruw(ι). Thus, the presence of additional peaks (or the
increased intensity of peaks) of the autocorrelation function of the time warped audio
signal, when compared to the autocorrelation function of the original audio signal can be
used as an indication of the effectiveness (in terms of a bitrate reduction) of the time warp.
Fig. 3k shows a block schematic diagram of an energy compaction information provider
370 configured to receive a time warped time domain representation of the audio signal,
for example, the time warped signal 234e, 234k (where the spectral domain transform
234d, 234j and optionally the analysis windower 234b and 234h is omitted), and to
provide, on the basis thereof, an energy compaction information 374, which may take the
role of the energy compaction information 372. The energy compaction information
provider 370 of Fig. 3k comprises an autocorrelation calculator 371 configured to compute
the autocorrelation function Rtw(ι) of the time warped signal a(tw) over a predetermined
range of discrete values of x. The energy compaction information provider 370 also
comprises an autocorrelation summer 372 configured to sum a plurality of values of the
autocorrelation function Rtw(ι) (for example, over a predetermined range of discrete values
of ι) and to provide the obtained sum as the energy compaction information 122, 234m,
234n.
Thus, the energy compaction information provider 370 allows the provision of a reliable
information indicating the efficiency of the time warp without actually performing the
spectral domain transformation of the time warped time domain version of the input audio
signal 210. Therefore, it is possible to perform a spectral domain transformation of the time
warped version of the input audio signal 310 only if it is found, on the basis of the energy
compaction information 122, 234m, 234n provided by the energy compaction information
provider 370, that the time warp actually brings along an improved encoding efficiency.

To summarize the above, embodiments according to the invention create a concept for a
final quality check. A resulting pitch contour (used in a time warp audio signal encoder) is
evaluated in terms of its coding gain and either accepted or rejected. Several measurements
concerning the sparsity of the spectrum or the coding gain may be taken into account for
this decision, for example, a spectral flatness measure, a band-wise segmental spectral
flatness measure, and/or a perceptual entropy.
The usage of different spectral compaction information has been discussed, for example,
the usage of a spectral flatness measure, the usage of a perceptual entropy measure, and the
usage of a time domain autocorrelation measure. Nevertheless, there are other measures
that show a compaction of the energy in a time warped spectrum.
All these measures can be used. Preferably, for all these measures, a ratio between the
measure for an unwarped and a time warped spectrum is defined, and a threshold is set for
this ratio in the encoder to determine if an obtained time warp contour has benefit in the
encoding or not.
All these measures may be applied to a full frame, where only the third portion of the pitch
contour is new (wherein, for example, three portions of the pitch contour are associated
with the full frame), or preferably only for the portion of the signal, for which this new
portion was obtained, for example, using a transform with a low overlap window centered
on the (respective) signal portion.
Naturally, a single measure or a combination of the above-mentioned measures may be
used, as desired.
Fig. 4a shows a flow chart of a method for providing a time warp activation signal on the
basis of an audio signal. The method 400 of Fig. 4a comprises a step 410 of providing an
energy compaction information describing a compaction of energy in a time-warp
transformed spectral representation of the audio signal. The method 400 further comprises
a step 420 of comparing the energy compaction information with a reference value. The
method 400 also comprises a step 430 of providing the time warp activation signal in
dependence on the result of the comparison.
The method 400 can be supplemented by any of the features and functionalities described
herein with respect to the provision of the time warp activation signal.

Fig. 4b shows a flow chart of a method for encoding an input audio signal to obtain an
encoded representation of the input audio signal. The method 450 optionally comprises a
step 460 of providing a time warp transformed spectral representation on the basis of the
input audio signal. The method 450 also comprises a step 470 of providing a time warp
activation signal. The step 470 may, for example, comprise the functionality of the method
400. Thus, the energy compaction information may be provided such that the energy
compaction information describes a compaction of energy in the time warp transformed
spectrum representation of the input audio signal. The method 450 also comprises a step
480 of selectively providing, in dependence on the time warp activation signal, a
description of the time warp transformed spectral representation of the input audio signal
using a newly found time warp contour information or description of a non-time-warp-
transformed spectral representation of the input audio signal using a standard (non-
varying) time warp contour information for inclusion into the encoded representation of the
input audio signal.
The method 450 can be supplemented by any of the features and functionalities discussed
herein with respect to the encoding of the input audio signal.
Fig. 5 illustrates a preferred embodiment of an audio encoder in accordance with the
present invention, in which several aspects of the present invention are implemented. An
audio signal is provided at an encoder input 500. This audio signal will typically be a
discrete audio signal which has been derived from an analog audio signal using a sampling
rate which is also called the normal sampling rate. This normal sampling rate is different
from a local sampling rate generated in a time warping operation, and the normal sampling
rate of the audio signal at input 500 is a constant sampling rate resulting in audio samples
separated by a constant time portion. The signal is put into an analysis windower 502,
which is, in this embodiment, connected to a window function controller 504. The analysis
windower 502 is connected to a time warper 506. Depending on the implementation,
however, the time warper 506 can be placed - in a signal processing direction - before the
analysis windower 502. This implementation is preferred, when a time warping
characteristic is required for analysis windowing in block 502, and when the time warping
operation is to be performed on time warped samples rather than unwarped samples.
Specifically in the context of MDCT-based time warping as described in Bernd Edler et al.,
"Time Warped MDCT", International Patent Application PCT/EP2009/002118. For other
time warping applications such as described in L. Villemoes, "Time Warped Transform
Coding of Audio Signals", PCT/EP2006/010246, Int. patent application, November 2005.,
the placement between the time warper 506 and the analysis windower 502 can be set as
required. Additionally, a time/frequency converter 508 is provided for performing a

time/frequency conversion of a time warped audio signal into a spectral representation.
The spectral representation can be input into a TNS (temporal noise shaping) stage 510,
which provides, as an output 510a, TNS information and, as an output 510b, spectral
residual values. Output 510b is coupled to a quantizer and coder block 512 which can be
controlled by a perceptual model 514 for quantizing a signal so that the quantization noise
is hidden below the perceptual masking threshold of the audio signal.
Additionally, the encoder illustrated in Fig. 5a comprises a time warp analyzer 516, which
may be implemented as a pitch tracker, which provides a time warping information at
output 518. The signal on line 518 may comprise a time warping characteristic, a pitch
characteristic, a pitch contour, or an information, whether the signal analyzed by the time
warp analyzer is a harmonic signal or a non-harmonic signal. The time warp analyzer can
also implement the functionality for distinguishing between voiced speech and unvoiced
speech. However, depending on the implementation, and whether a signal classifier 520 is
implemented, the voiced/unvoiced decision can also be done by the signal classifier 520. In
this case, the time warp analyzer does not necessarily have to perform the same
functionality. The time warp analyzer output 518 is connected to at least one and
preferably more than one functionalities in the group of functionalities comprising the
window function controller 504, the time warper 506, the TNS stage 510, the quantizer and
coder 512 and an output interface 522.
Analogously, an output 522 of the signal classifier 520 can be connected to one or more of
the functionalities of a group of functionalities comprising the window function controller
504, the TNS stage 510, a noise filling analyzer 524 or the output interface 522.
Additionally, the time warp analyzer output 518 can also be connected to the noise filling
analyzer 524.
Although Fig. 5a illustrates a situation, where the audio signal on analysis windower input
500 is input into the time warp analyzer 516 and the signal classifier 520, the input signals
for these functionalities can also be taken from the output of the analysis windower 502
and, with respect to the signal classifier, can even be taken from the output of the time
warper 506, the output of the time/frequency converter 508 or the output of the TNS stage
510.
In addition to a signal output by the quantizer encoder 512 indicated at 526, the output
interface 522 receives the TNS side information 510a, a perceptual model side information
528, which may include scale factors in encoded form, time warp indication data for more
advanced time warp side information such as the pitch contour on line 518 and signal

classification information on line 522. Additionally, the noise filling analyzer 524 can also
output noise filling data on output 530 into the output interface 522. The output interface
522 is configured for generating encoded audio output data on line 532 for transmission to
a decoder or for storing in a storage device such as memory device. Depending on the
implementation, the output data 532 may include all of the input into the output interface
522 or may comprise less information, provided that the information is not required by a
corresponding decoder, which has a reduced functionality, or provided that the information
is already available at the decoder due to a transmission via a different transmission
channel.
The encoder illustrated in Fig. 5a may be implemented as defined in detail in the MPEG-4
standard apart from additional functionalities illustrated in the inventive encoder in Fig. 5a
represented by the window function controller 504, the noise filling analyzer 524, the
quantizer encoder 512 and the TNS stage 510, which have, compared to the MPEG-4
standard, an advanced functionality. A further description is in the AAC standard
(international standard 13818-7) or 3GPP TS 26.403 V7.0.0: Third generation partnership
project; technical specification group services and system aspect; general audio codec
audio processing functions; enhanced AAC plus general audio codec.
' Subsequently, Fig. 5b is discussed, which illustrates a preferred embodiment of an audio
decoder for decoding an encoded audio signal received via input 540. The input interface
540 is operative to process the encoded audio signal so that the different information items
of information are extracted from the signal on line 540. This information comprises signal
classification information 541, time warp information 542, noise filling data 543, scale
factors 544, TNS data 545 and encoded spectral information 546. The encoded spectral
information is input into an entropy decoder 547, which may comprise a Huffman decoder
or an arithmetic decoder, provided that the encoder functionality in block 512 in Fig. 5a is
implemented as a corresponding encoder such as a Huffman encoder or an arithmetic
encoder. The decoded spectral information is input into a re-quantizer 550, which is
connected to a noise filler 552. The output of the noise filler 552 is input into an inverse
TNS stage 554, which additionally receives the TNS data on line 545. Depending on the
implementation, the noise filler 552 and the TNS stage 554 can be applied in different
order so that the noise filler 552 operates on the TNS stage 554 output data rather than on
the TNS input data. Additionally, a frequency/time converter 556 is provided, which feeds
a time dewarper 558. At the output of the signal processing chain, a synthesis windower
preferably performing an overlap/add processing is applied as indicated at 560. The order
of the time dewarper 558 and the synthesis stage 560 can be changed, but, in the preferred

embodiment, it is preferred to perform an MDCT-based encoding/decoding algorithm as
defined in the AAC standard (AAC = advanced audio coding). Than, the inherent cross-
fade operation from one block to the next due to the overlap/add procedure is
advantageously used as the last operation in the processing chains so that all blocking
artifacts are effectively avoided.
Additionally, a noise filling analyzer 562 is provided, which is configured for controlling
the noise filler 552 and which receives as an input, time warp information 542 and/or
signal classification information 541 and information on the re-quantized spectrum, as the
case may be.
Preferably, all functionalities described hereafter are applied together in an enhanced audio
encoder/decoder scheme. Nevertheless, the functionalities described hereafter can also be
applied independently on each other, i.e., so that only one or a group, but not all of the
functionalities are implemented in a certain encoder/decoder scheme.
Subsequently, the noise filling aspect of the present invention is described in detail.
In an embodiment, the additional information provided by the time warping/pitch contour
tool 516 in Fig. 5a is used beneficially for controlling other codec tools and, specifically,
the noise filling tool implemented by the noise filling analyzer 524 on the encoder side
and/or implemented by the noise filling analyzer 562 and the noise filler 552 on the
decoder side.
Several encoder tools within the AAC frame work such as a noise filling tool are
controlled by information gathered by the pitch contour analysis and/or by an additional
knowledge of a signal classification provided by the signal classifier 520.
A found pitch contour indicates signal segments with a clear harmonic structure, so the
noise filling in between the harmonic lines might decrease the perceived quality, especially
on speech signals, therefore the noise level is reduced, when a pitch contour is found.
Otherwise, there would be noise between the partial tones, which has the same effect as the
increased quantization noise for a smeared spectrum. Furthermore, the amount of the noise
level reduction can be further refined by using the signal classifier information, so e.g. for
speech signals there would be no noise filling and a moderate noise filling would be
applied to generic signals with a strong harmonic structure.

Generally, the noise filler 552 is useful for inserting spectral lines into a decoded spectrum,
where zeroes have been transmitted from an encoder to a decoder, i.e., where the quantizer
512 in Fig. 5a has quantized spectral lines to zero. Naturally, quantizing spectral lines to
zero greatly reduced the bitrate of the transmitted signal, and, in theory, the elimination of
these (small) spectral lines is not audible, when these spectral lines are below the
perceptual masking threshold as determined by the perceptual model 514. Nevertheless, it
has been found that these "spectral holes", which can include many adjacent spectral lines
result in a quite unnatural sound. Therefore, a noise filling tool is provided for inserting
spectral lines at positions, where lines have been quantized to zero by an encoder-side
quantizer. These spectral lines may have a random amplitude or phase, and these decoder-
side synthesized spectral lines are scaled using a noise filling measure determined on the
encoder-side as illustrated in Fig. 5 a or depending on a measure determined on the
decoder-side as illustrated in Fig. 5b by optional block 562. The noise filling analyzer 524
in Fig. 5a is, therefore, configured for estimating a noise filling measure of an energy of
audio values quantized to zero for a time frame of the audio signal.
In an embodiment of the present invention, the audio encoder for encoding an audio signal
on line 500 comprises the quantizer 512 which is configured for quantizing audio values,
where the quantizer 512 is furthermore configured to quantize to zero audio values below a
quantization threshold. This quantization threshold may be the first step of a step-based
quantizer, which is used for the decision, whether a certain audio value is quantized to
zero, i.e., to a quantization index of zero, or is quantized to one, i.e., a quantization index
of one indicating that the audio value is above this first threshold. Although the quantizer
in Fig. 5a is illustrated as performing the quantization of frequency domain values, the
quantizer can also be used for quantizing time domain values in an alternative
embodiment, in which the noise filling is performed in the time domain rather than the
frequency domain.
The noise filling analyzer 524 is implemented as a noise filling calculator for estimating a
noise filling measure of an energy of audio values quantized to zero for a time frame of the
audio signal by the quantizer 512. Additionally, the audio encoder comprises an audio
signal analyzer 600 illustrated in Fig. 6a, which is configured for analyzing, whether the
time frame of the audio signal has a harmonic characteristic or a speech characteristic. The
signal analyzer 600 can, for example, comprise block 516 of Fig. 5a or block 520 of Fig.
5a or can comprise any other device for analyzing, whether a signal is a harmonic signal or
a speech signal. Since the time warp analyzer 516 is implemented to always look for a
pitch contour, and since the presence of a pitch contour indicates a harmonic structure of

the signal, the signal analyzer 600 in Fig. 6a can be implemented as a pitch tracker or a
time warping contour calculator of a time warp analyzer.
The audio encoder additionally comprises a noise filling level manipulator 602 illustrated
in Fig. 6a, which outputs a manipulated noise filling measure/level to be output to the
output interface 522 indicated at 530 in Fig. 5a. The noise filling measure manipulator 602
is configured for manipulating the noise filling measure depending on the harmonic or
speech characteristic of the audio signal. The audio encoder additionally comprises the
output interface 522 for generating an encoded signal for transmission or storage, the
encoded signal comprising the manipulated noise filling measure output by block 602 on
line 530. This value corresponds to the value output by block 562 in the decoder-side
implementation illustrated in Fig. 5b.
As indicated in Fig. 5a and Fig. 5b, the noise filling level manipulation can either be
implemented in an encoder or can be implemented in a decoder or can be implemented in
both devices together. In a decoder-side implementation, the decoder for decoding an
encoded audio signal comprises the input interface 539 for processing the encoded signal
on line 540 to obtain a noise filling measure, i.e., the noise filling data on line 543, and
encoded audio data on line 546. The decoder additionally comprises a decoder 547 and re-
quantizer 550 for generating re-quantized data.
Additionally, the decoder comprises a signal analyzer 600 (Fig. 6a) which may be
implemented in the noise filling analyzer 562 in Fig. 5b for retrieving information, whether
a time frame of the audio data has a harmonic or speech characteristic.
Additionally, the noise filler 552 is provided for generating noise filling audio data,
wherein the noise filler 552 is configured to generate the noise filling data in response to
the noise filling measure transmitted via the encoded signal and generated by the input
interface at line 543 and the harmonic or speech characteristic of the audio data as defined
by the signal analyzers 516 and/or 550 on the encoder side or as defined by item 562 on the
decoder side via processing and interpreting the time warp information 542 indicating,
whether a certain time frame has been subjected to a time warping processing or not.
Additionally, the decoder comprises a processor for processing the re-quantized data and
the noise filling audio data to obtain a decoded audio signal. The processor may include
items 554, 556, 558, 560 in Fig. 5b as the case may be. Additionally, depending on the
specific implementation of the encoder/decoder algorithm, the processor can include other

processing blocks, which are provided, for example, in a time domain encoder such as the
AMR WB+ encoder or other speech coders.
The inventive noise filling manipulation can, therefore, be implemented on the encoder
side only by calculating the straightforward noise measure and by manipulating this noise
measure based on harmonic/speech information and by transmitting the already correct
manipulated noise filling measure which can then be applied by a decoder in a
straightforward manner. Alternatively, the non-manipulated noise filling measure can be
transmitted from an encoder to a decoder, and the decoder will then analyze, whether the
actual time frame of an audio signal has been time warped, i.e., has a harmonic or speech
characteristic so that the actual manipulation of the noise filling measure takes place on the
decoder-side.
Subsequently, Fig. 6b is discussed in order to explain preferred embodiments for
manipulating the noise level estimate.
In the first embodiment, a normal noise level is applied, when the signal does not have an
harmonic or speech characteristic. This is the case, when no time warp is applied. When,
additionally, a signal classifier is provided, then the signal classifier distinguishing
between speech and no speech would indicate no speech for the situation, where time warp
was not active, i.e., where no pitch contour was found.
When, however, the time warp was active, i.e., when a pitch contour was found, which
indicates an harmonic content, then the noise filling level would be manipulated to be
lower than in the normal case. When an additional signal classifier is provided, and then
this signal classifier indicates speech, and when concurrently the time warp information
indicates a pitch contour, then a lower or even zero noise filling level is signaled. Thus, the
noise filling level manipulator 602 of Fig. 6a will reduce the manipulated noise level to
zero or at least to a value lower than the low value indicated in Fig. 6b. Preferably, the
signal classifier additionally has a voiced/unvoiced detector as indicated in the left of Fig.
6b. In the case of voiced speech, a very low or zero noise filling level is signaled/applied.
However, in the case of unvoiced speech, where the time warp indication does not indicate
a time warp processing due to the fact that no pitch was found, but where the signal
classifier signals speech content, the noise filling measure is not manipulated, but a normal
noise filling level is applied.
Preferably, the audio signal analyzer comprises a pitch tracker for generating an indication
of the pitch such as a pitch contour or an absolute pitch of a time frame of the audio signal.

Then, the manipulator is configured for reducing the noise filling measure when a pitch is
found, and to not reduce the noise filling measure when a pitch is not found.
As indicated in Fig. 6a, a signal analyzer 600 is, when applied to the decoder-side, not
performing an actual signal analysis like a pitch tracker or a voiced/unvoiced detector, but
the signal analyzer parses the encoded audio signal in order to extract a time warp
information or a signal classification information. Therefore, the signal analyzer 600 may
be implemented within the input interface 539 in the Fig. 5b decoder.
A further embodiment of the present invention will be subsequently discussed with respect
to Figs. 7a-7e.
For onsets of speech where a voiced speech part begins after a relative silent signal portion,
the block switching algorithm might classify it as an attack and might chose short blocks
for this particular frame, with a loss of coding gain on the signal segment that has a clear
harmonic structure. Therefore, the voiced/unvoiced classification of the pitch tracker is
used to detect voiced onsets and prevent the block switching algorithm from indicating a
transient attack around the found onset. This feature may also be coupled with the signal
classifier to prevent block switching on speech signals and allow them for all other signals.
Furthermore a finer control of the block switching might be implemented by not only allow
or disallow the detection of attacks, but use a variable threshold for attack detection based
on the voiced onset and signal classification information. Furthermore, the information can
be used to detect attacks like the above mentioned voiced onsets but instead of switching to
short blocks, use long windows with short overlaps, which remain the preferable spectral
resolution but decrease the time region where pre and post echoes may arise. Fig. 7d shows
the typical behavior without the adaptation, Fig. 7e shows two different possibilities of
adaptation (prevention and low overlap windows).
An audio encoder in accordance with an embodiment of the present invention operates for
generating an audio signal such as the signal output by output interface 522 from Fig. 5a.
The audio encoder comprises an audio signal analyzer such as the time warp analyzer 516
or a signal classifier 520 of Fig. 5a. Generally, the audio signal analyzer analyzes whether
a time frame of the audio signal has a harmonic or speech characteristic. To this end, the
signal classifier 520 of Fig. 5a may include a voiced/unvoiced detector 520a or a speech/no
speech detector 520b. Although not shown in Fig. 7a, a time warp analyzer such as the
time warp analyzer 516 of Fig. 5a, which can include a pitch tracker can also be provided
instead of items 520a and 520b or in addition to these functionalities. Additionally, the
audio encoder comprises the window function controller 504 for selecting a window

function depending on a harmonic or speech characteristic of the audio signal as
determined by the audio signal analyzer. The windower 502 then windows the audio signal
or, depending on the certain implementation, the time warped audio signal using the
selected window function to obtain a windowed frame. This window frame is, then, further
processed by a processor to obtain an encoded audio signal. The processor can comprise
items 508, 510, 512 illustrated in Fig. 5a or more or less functionalities of well-known
audio encoders such as transform based audio encoders or time domain-based audio
encoders which comprise an LPC filter such as speech coders and, specifically, speech
coders implemented in accordance with the AMR-WB+ standard.
In a preferred embodiment, the window function controller 504 comprises a transient
detector 700 for detecting a transient in the audio signal, wherein the window function
controller is configured for switching from a window function for a long block to a
window function for a short block, when a transient is detected and a harmonic or speech
characteristic is not found by the audio signal analyzer. When, however, a transient is
detected and a harmonic or speech characteristic is found by the audio signal analyzer, then
the window function controller 504 does not switch to the window function for the short
block. Window function outputs indicating a long window when no transient is obtained
and a short window when a transient is detected by the transient detector are illustrated as
701 and 702 in Fig. 7a. This normal procedure as performed by the well-known AAC
encoder is illustrated in Fig. 7d. At the position of the voice onset, transient detector 700
detects an increase of energy from one frame to the next frame and, therefore, switches
from a long window 710 to short windows 712. In order to accommodate this switch, a
long stop window 714 is used, which has a first overlapping portion 714a, a non-aliasing
portion 714b, a second shorter overlap portion 714c and a zero portion extending between
point 716 and the point on the time axis indicated by 2048 samples. Then, the sequence of
short windows indicated at 712 is performed which is, then, ended by a long start window
718 having a long overlapping portion 718a overlapping with the next long window not
illustrated in Fig. 7d. Furthermore, this window has a non-aliasing portion 718b, a short
overlap portion 718c and a zero portion extending between point 720 on the time axis until
the 2048 point. This portion is a zero portion.
Normally, the switching over to short windows is useful in order to avoid pre-echoes
which would occur within a frame before the transient event which is the position of the
voiced onset or, generally, the beginning of the speech or the beginning of a signal having
a harmonic content. Generally, a signal has a harmonic content, when a pitch tracker
decides that the signal has a pitch. Alternatively, there are other harmonicity measures such
as a tonality measure above a certain minimum level together with a characteristic that

prominent peaks are in a harmonic relation to each other. A plurality of further techniques
exist to determine, whether a signal is harmonic or not.
A disadvantage of short windows is that the frequency resolution is decreased, since the
time resolution is increased. For high quality encoding of speech and, specifically, voiced
speech portions or portions having a strong harmonic content, a good frequency resolution
is desired. Therefore, the audio signal analyzer illustrated at 516, 520 or 520a, 520b is
operative to output a deactivate signal to the transient detector 700 so that a switch over to
short windows is prevented when a voiced speech segment or a signal segment having a
strong harmonic characteristic is detected. This ensures that, for coding such signal
portions, a high frequency resolution is maintained. This is a trade off between pre-echoes
on the one hand and high quality and high resolution encoding of the pitch for the speech
signal or the pitch for a harmonic non-speech signal on the other hand. It has been found
out that it is much more disturbing when the harmonic spectrum is not encoded accurately
compared to any pre-echoes which would occur. In order to furthermore decrease the pre-
echoes, a TNS processing is favored for such a situation, which will be discussed in
connection with Figs. 8a and 8b.
In an alternative embodiment illustrated in Fig. 7b, the audio signal analyzer comprises a
voiced/unvoiced and/or speech/non-speech detector 520a, 520b. However, the transient
detector 700 included in the window function controller is not fully activated/deactivated
as in Fig. 7a, but the threshold included in the transient detector is controlled using a
threshold control signal 704. In this embodiment, the transient detector 700 is configured
for determining a quantitative characteristic of the audio signal and for comparing the
quantitative characteristic to the controllable threshold, wherein a transient is detected
when the quantitative characteristic has a predetermined relation to the controllable
threshold. The quantitative characteristic can be a number indicating the energy increase
from one block to the next block, and the threshold can be a certain threshold energy
increase. When the energy increase from one block to the next is higher than the threshold
energy increase, then a transient is detected, so that, in this case, the predetermined relation
is a "greater than" relation. In other embodiments, the predetermined relation can also be a
"lower than" relation, for example when the quantitative characteristic is an inverted
energy increase. In the Fig. 7b embodiment, the controllable threshold is controlled so that
the likelihood for a switch to a window function for a short block is reduced, when the
audio signal analyzer has found a harmonic or speech characteristic. In the energy increase
embodiment, the threshold control signal 704 will result in an increase of the threshold so
that switches to short blocks occur only when the energy increase from one block to the
next is a particularly high energy increase.

In an alternative embodiment, the output signal from the voiced/unvoiced detector 520a or
the speech/no speech detector 520b can also be used to control the window function
controller 504 in such a way that instead of switching over to a short block at a speech
onset, switching over to a window function which is longer than the window function for
the short block is performed. This window function ensures a higher frequency resolution
than a short window function, but has a shorter length than the long window function so
that a good comprise between pre-echoes on the one hand and a sufficient frequency
resolution on the other hand is obtained. In an alternative embodiment, a switch over to a
window function having a smaller overlap can be performed as indicated by the hatched
line in Fig. 7e at 706. The window function 706 has a length of 2048 samples as the long
block, but this window has a zero portion 708 and a non-aliasing portion 710 so that a short
overlap length 712 from window 706 to a corresponding window 707 is obtained. The
window function 707, again, has a zero portion left of region 712 and a non-aliasing
portion to the right of region 712 in analogy to window function 710. This low-overlap
embodiment, effectively results in shorter time length for reducing pre-echoes due to the
zero portion of window 706 and 707, but on the other hand has a sufficient length due to
the overlap portion 714 and the non-aliasing portion 710 so that a sufficiently enough
frequency resolution is maintained.
In the preferred MDCT implementation as implemented by the AAC encoder, maintaining
a certain overlap provides the additional advantage that, on the decoder side, an
overlap/add processing can be performed which means that a kind of cross-fading between
blocks is performed. This effectively avoids blocking artifacts. Additionally, this
overlap/add feature provides the cross-fading characteristic without increasing the bitrate,
i.e., a critically sampled cross-fade is obtained. In regular long windows or short windows,
the overlap portion is a 50% overlap as indicated by the overlapping portion 714. In the
embodiment where the window function is 2048 samples long, the overlap portion is 50%,
i.e., 1024 samples. The window function having a shorter overlap which is to be used for
effectively windowing a speech onset or an onset of a harmonic signal is preferably less
than 50% and is, in the Fig. 7e embodiment, only 128 samples, which is 1/16 of the whole
window length. Preferably, overlap portions between 1/4 and 1/32 of the whole window
function length are used.
Fig. 7c illustrates this embodiment, in which an exemplary voiced/unvoiced detector 520a
controls a window shape selector included in the window function controller 504 in order
to either select a window shape with a short overlap as indicated at 749 or a window shape
with a long overlap as indicated at 750. The selection of one of both shapes is

implemented, when the voiced/unvoiced detector 500a issues a voiced detected signal at
751, where the audio signal used for analysis can be the audio signal at input 500 in Fig. 5a
or a pre-processed audio signal such as a time warped audio signal or an audio signal
which has been subjected to any other pre-processing functionality. Preferably, the window
shape selector 504 in Fig. 7c which is included in the window function controller 504 in
Fig. 5a only uses the signal 751, when a transient detector included in the window function
controller would detect a transient and would command a switch from a long window
function to a short window function as discussed in connection with Fig. 7a.
Preferably, the window function switching embodiment is combined with a temporal noise
shaping embodiment discussed in connection with Figs. 8a and 8b. However, the TNS
(temporal noise shaping) embodiment can also be implemented without the block
switching embodiment.
The spectral energy compaction property of the time warped MDCT also influences the
temporal noise shaping (TNS) tool, since the TNS gain tends to decrease for time warped
frames especially for some speech signals. Nevertheless it is desirable to activate TNS, e.g.
to reduce pre-echoes on voiced onsets or offsets (cf. block switching adaption), where no
block switching is desired but still the temporal envelope of the speech signal exhibits
rapid changes. Typically, an encoder uses some measure to see if the application of the
TNS is fruitful for a certain frame, e.g. the prediction gain of the TNS filter when applied
to the spectrum. So a variable TNS gain threshold is preferred, which is lower for segments
with an active pitch contour, so that it is ensured that TNS is more often active for such
critical signal portions like voiced onsets. As with the other tools, this may also be
complemented by taking the signal classification into account.
The audio encoder in accordance with this embodiment for generating an audio signal
comprises a controllable time warper such as time warper 506 for time warping the audio
signal to obtain a time warped audio signal. Additionally, a time/frequency converter 508
for converting at least a portion of the time warped audio signal into a spectral
representation is provided. The time/frequency converter 508 preferably implements an
MDCT transform as known from the AAC encoder, but the time/frequency converter can
also perform any other kind of transforms such as a DCT, DST, DFT, FFT or MDST
transform or can comprise a filter bank such as a QMF filter bank.
Additionally, the encoder comprises a temporal noise shaping stage 510 for performing a
prediction filtering over frequency of the spectral representation in accordance with the

temporal noise shaping control instruction, wherein the prediction filtering is not
performed, when the temporal noise shaping control instruction does not exist.
Additionally, the encoder comprises a temporal noise shaping controller for generating the
temporal noise shaping control instruction based on the spectral representation.
Specifically, the temporal noise shaping controller is configured for increasing the
likelihood for performing the prediction filtering over frequency, when the spectral
representation is based on a time warped time signal or for decreasing the likelihood for
performing the prediction filtering over frequency, when the spectral representation is not
based on a time warped time signal. Specifics of the temporal noise shaping controller are
discussed in connection with Fig. 8.
The audio encoder additionally comprises a processor for further processing a result of the
prediction filtering over frequency to obtain the encoded signal. In an embodiment, the
processor comprises the quantizer encoder stage 512 illustrated in Fig. 5 a.
A TNS stage 510 illustrated in Fig. 5a is illustrated in detail in Fig. 8. Preferably, the
temporal noise shaping controller included in stage 510 comprises a TNS gain calculator
800, a subsequently connected TNS decider 802 and a threshold control signal generator
804. Depending on a signal from the time warp analyzer 516 or the signal classifier 520 or
both, the threshold control signal generator 804 outputs a threshold control signal 806 to
the TNS decider. The TNS decider 802 has a controllable threshold, which is increased or
decreased in accordance with the threshold control signal 806. The threshold in the TNS
decider 802 is, in this embodiment, a TNS gain threshold. When the actually calculated
TNS gain output by block 800 exceeds the threshold, then the TNS control instruction
requires a TNS processing as output, while, in the other case when the TNS gain is below
the TNS gain threshold, no TNS instruction is output or a signal is output which instructs
that the TNS processing is not useful and is not to be performed in this specific time frame.
The TNS gain calculator 800 receives, as an input, the spectral representation derived from
the time warped signal. Typically, a time warped signal will have a lower TNS gain, but on
the other hand, a TNS processing due to the temporal noise shaping feature in the time
domain is beneficiary in the specific situation, where there is a voiced/harmonic signal
which has been subjected to a time warping operation. On the other hand, the TNS
processing is not useful in situations, where the TNS gain is low, which means that the
TNS residual signal at line 510b has the same or a higher energy as the signal before the
TNS stage 510. In a situation, where the energy of the TNS residual signal on line 51 Od is

slightly lower than the energy before the TNS stage 510, the TNS processing might also
not be of advantage, since the bit reduction due to the slightly smaller energy in the signal
which is efficiently used by the quantizer/entropy encoder stage 512 is smaller than the bit
increase introduced by the necessary transmission of the TNS side information indicated at
510a in Fig. 5a. Although one embodiment automatically switches on the TNS processing
for all frames, in which a time warped signal is input indicated by the pitch information
from block 516 or the signal classifier information from block 520, a preferred
embodiment also maintains the possibility to deactivate TNS processing, but only when the
gain is really low or at least lower than in the normal case, when no harmonic/speech
signal is processed.
Fig. 8b illustrates an implementation where three different threshold settings are
implemented by the threshold control signal generator 804/TNS decider 802. When a pitch
contour does not exist, and when a signal classifier indicates an unvoiced speech or no
speech at all, then the TNS decision threshold is set to be in a normal state requiring a
relatively high TNS gain for activating TNS. When, however, a pitch contour is detected,
but the signal classifier indicates no speech or the voiced/unvoiced detector detects an
unvoiced speech, then the TNS decision threshold is set to a lower level, which means that
even when comparatively low TNS gains are calculated by block 800 in Fig. 8a,
nevertheless the TNS processing is activated.
In a situation, in which an active pitch contour is detected and in which voiced speech is
found, then, the TNS decision threshold is set to the same lower value or is set to an even
lower state so that even small TNS gains are sufficient for activating a TNS processing.
In an embodiment, the TNS gain controller 800 is configured for estimating a gain in bit
rate or quality, when the audio signal is subjected to the prediction filtering over frequency.
A TNS decider 802 compares the estimated gain to a decision threshold, and a TNS control
information in favor of the prediction filtering is output by block 802, when the estimated
gain is in a predetermined relation to the decision threshold, where this predetermined
relation can be a "greater than" relation, but can also be a "lower than" relation for an
inverted TNS gain for example. As discussed, the temporal noise shaping controller is
furthermore configured for varying the decision threshold preferably using the threshold
control signal 806 so that, for the same estimated gain, the prediction filtering is activated,
when the spectral representation is based on the time warped audio signal, and is not
activated, when the spectral representation is not based on the time warped audio signal.

Normally, voiced speech will exhibit a pitch contour, and unvoiced speech such as
fricatives or sibilants will not exhibit a pitch contour. However, there do exist non-speech
signals, which strong harmonic content and, therefore, have a pitch contour, although the
speech detector does not detect speech. Additionally, there exist certain speech over music
or music over speech signals, which are determined by the audio signal analyzer (516 of
Fig. 5a for example) to have an harmonic content, but which are not detected by the signal
classifier 520 as being a speech signal. In such a situation, all processing operations for
voiced speech signals can also be applied and will also result in an advantage.
Subsequently, a further preferred embodiment of the present invention with respect to an
audio encoder for encoding an audio signal is described. This audio encoder is specifically
useful in the context of bandwidth extension, but is also useful in stand alone encoder
applications, where the audio encoder is set to code a certain number of lines in order to
obtain a certain bandwidth limitation/low-pass filtering operation. In non-time-warped
applications, this bandwidth limitation by selecting a certain predetermined number of
lines will result in a constant bandwidth, since the sampling frequency of the audio signal
is constant. In situations, however, in which a time warp processing such as by block 506
in Fig. 5 a is performed, an encoder relying on a fixed number of lines will result in a
varying bandwidth introducing strong artifacts not only perceivable by trained listeners but
also perceivable by untrained listeners.
The AAC core coder normally codes a fixed number of lines, setting all others above the
maximum line to zero. In the unwarped case this leads to a low-pass effect with a constant
cut-off frequency and therefore a constant bandwidth of the decoded AAC signal. In the
time warped case the bandwidth varies due to the variation of the local sampling
frequency, a function of the local time warping contour, leading to audible artifacts. The
artifacts can be reduced by adaptively choosing the number of lines - as a function of the
local time warping contour and its obtained average sampling rate - to be coded in the core
coder depending on the local sampling frequency such that a constant average bandwidth is
obtained after time re-warping in the decoder for all frames. An additional benefit is bit
saving in the encoder.
The audio encoder in accordance with this embodiment comprises the time warper 506 for
time warping an audio signal using a variable time warping characteristic. Additionally, a
time/frequency converter 508 for converting a time warped audio signal into a spectral
representation having a number of spectral coefficients is provided. Additionally, a
processor for processing a variable number of spectral coefficients to generate the encoded
audio signal is used, where this processor comprising the quantizer/coder block 512 of Fig.

5a is configured for setting a number of spectral coefficients for a frame of the audio signal
based on the time warping characteristic for the frame so that a bandwidth variation
represented by the processed number of frequency coefficients from frame to frame is
reduced or eliminated.
The processor implemented by block 512 may comprise a controller 1000 for controlling
the number of lines, where the result of the controller 1000 is that, with respect to a
number of lines set for the case of a time frame being encoded without any time warping, a
certain variable number of lines is added or discarded at the upper end of the spectrum.
Depending on the implementation, the controller 1000 can receive a pitch contour
information in a certain frame 1001 and/or a local average sampling frequency in the frame
indicated at 1002.
In the Figs. 9(a) to 9(e), the right pictures illustrate a certain bandwidth situation for certain
pitch contours over a frame, where the pitch contours over the frame are illustrated in the
respective left pictures for the time warp and are illustrated in the medium pictures after
the time warp, where a substantially constant pitch characteristic is obtained. This is the
target of the time warping functionality that, after time warping, the pitch characteristic is
as constant as possible.
The bandwidth 900 illustrates the bandwidth which is obtained when a certain number of
lines output by a time/frequency converter 508 or output by a TNS stage 510 of Fig. 5a is
taken, and when a time warping operation is not performed, i.e., when the time warper 506
was deactivated, as indicated by the hatched line 507. When, however, a non-constant time
warp contour is obtained, and when this time warp contour is brought to a higher pitch
inducing a sampling rate increase (Fig. 9(a), (c)) the bandwidth of the spectrum decreases
with respect to a normal, non-time-warped situation. This means that the number of lines to
be transmitted for this frame has to be increased in order to balance this loss of bandwidth.
Alternatively, bringing the pitch to a lower constant pitch illustrated in Fig. 9(b) or Fig.
9(d) results in a sampling rate decrease. The sampling rate decrease results in a bandwidth
increase of the spectrum of this frame with respect to the linear scale, and this bandwidth
increase has to be balanced using a deletion or discarding of a certain number of lines with
respect to the value of number of lines for the normal non-time-warped situation.
Fig. 9(e) illustrates a special case, in which a pitch contour is brought to a medium level so
that the average sampling frequency within a frame is, instead of performing the time
warping operation, the same as the sampling frequency without any time warping. Thus,

the bandwidth of the signal is non-affected, and the straightforward number of lines to be
used for the normal case without time warping can be processed, although the time
warping operation is be performed. From Fig. 9, it becomes clear that performing a time
warping operation does not necessarily influence the bandwidth, but the influencing of the
bandwidth depends on the pitch contour and the way, how the time warp is performed in a
frame. Therefore, it is preferred to use, as the control value, a local or average sampling
rate. The determination of this local sampling rate is illustrated in Fig. 11. The upper
portion in Fig. 11 illustrates a time portion with equidistant sampling values. A frame
includes, for example, seven sampling values indicated by Tn in the upper plot. The lower
plot shows the result of a time warping operation, in which, altogether, a sampling rate
increase has taken place. This means that the time length of the time warped frame is
smaller than the time length of the non-time-warped frame. Since, however, the time length
of the time warped frame to be introduced into the time/frequency converter is fixed, the
case of a sampling rate increase causes that an additional portion of the time signal not
belonging to the frame indicated by Tn is introduced into the time warped frame as
indicated by lines 1100. Thus, a time warped frame covers a time portion of the audio
signal indicated by Tnn which is longer than the time Tn. In view of that, the effective
distance between two frequency lines or the frequency bandwidth of a single line in the
linear domain (which is the inverse value for the resolution) has decreased, and the number
of lines Nn set for a non-time-warped case when multiplied by the reduced frequency
distance results in a smaller bandwidth, i.e., a bandwidth decrease.
The other case, not illustrated in Fig. 11, where a sampling rate decrease is performed by
the time warper, the effective time length of a frame in the time warped domain is smaller
than the time length of the non-time-warped domain so that the frequency bandwidth of a
single line or the distance between two frequency lines has increased. Now, multiplying
this increased Af by the number NN of lines for the normal case will result in an increased
bandwidth due to the reduced frequency resolution/increased frequency distance between
two adjacent frequency coefficients.
Fig. 11 additionally illustrates, how an average sampling rate fsR is calculated. To this end,
the time distance between two time warped samples is determined and the inverse value is
taken, which is defined to be the local sampling rate between two time warped samples.
Such a value can be calculated between each pair of adjacent samples, and the arithmetic
mean value can be calculated and this value finally results in the average local sampling
rate, which is preferably used for being input into the controller 1000 of Fig. 10a.

Fig. 10b illustrates a plot indicating how many lines have to be added or discarded
depending on the local sampling frequency, where the sampling frequency fN for the
unwarped case together the number of lines NN for the non-time-warped case defines the
intended bandwidth, which should be kept constant as much as possible for a sequence of
time warped frames or for a sequence of time warped and non-time-warped frames.
Fig. 12b illustrates the dependence between the different parameters discussed in
connection with Fig. 9, Fig. 10b and Fig. 11. Basically, when the sampling rate, i.e., the
average sampling rate fsR decreases with respect to the non-time-warped case, lines have to
be deleted, while lines have to be added, when the sampling rate increases with respect to
the normal sampling rate fu for the non-time-warped case so that bandwidth variations
from frame to frame are reduced or preferably even eliminated as much as possible.
The bandwidth resulting by the number of lines NN and the sampling rate fN preferably
defines the cross-over frequency 1200 for an audio coder which, in addition to a source
core audio encoder, has a bandwidth extension encoder (BWE encoder). As known in the
art, a bandwidth extension encoder only codes a spectrum with a high bit rate until the
cross-over frequency and encodes the spectrum of the high band, i.e., between the cross-
over frequency 1200 and the frequency f\iAX with a low bit rate, where this low bit rate
typically is even lower than 1/10 or less of the bit rate required for the low band between a
frequency of 0 and the cross-over frequency 1200. Fig. 12a furthermore illustrates the
bandwidth BWAAC of a straightforward AAC audio encoder, which is much higher than the
cross-over frequency. Hence, lines can not only be discarded, but can be added as well.
Furthermore, the variation of the bandwidth for a constant number of lines depending on
the local sampling rate fsR is illustrated as well. Preferably, the number of lines to be added
or to be deleted with respect to the number of lines for the normal case is set so that each
frame of the AAC encoded data has a maximum frequency as close as possible to the
cross-over frequency 1200. Thus, any spectral holes due to a bandwidth reduction on the
one hand or an overhead by transmitting information on a frequency above the cross-over
frequency in the low band encoded frame are avoided. This, on the one hand, increases the
quality of the decoded audio signal and, on the other hand, decreases the bit rate.
The actual adding of lines with respect to a set number of lines or a deletion of lines with
respect to the set number of lines can be performed before quantizing the lines, i.e., at the
input of block 512, or can be performed subsequent to quantizing or can, depending on the
specific entropy code, also be performed subsequent to entropy coding.

Furthermore, it is preferred to bring the bandwidth variations to a minimum level and to
even eliminate the bandwidth variations, but, in other implementations, even a reduction of
bandwidth variations by determining the number of lines depending on the time warping
characteristic even increases the audio quality and decreases the required bit rate compared
to a situation, where a constant number of lines is applied irrespective of a certain time
warp characteristic.
Although some aspects have been described in the context of an apparatus, it is clear that
these aspects also represent a description of the corresponding method, where a block or
device corresponds to a method step or a feature of a method step. Analogously, aspects
described in the context of a method step also represent a description of a corresponding
block or item or feature of a corresponding apparatus.
Depending on certain implementation requirements, embodiments of the invention can be
implemented in hardware or in software. The implementation can be performed using a
digital storage medium, for example a floppy disk, a DVD, a CD, a ROM, a PROM, an
EPROM, an EEPROM or a FLASH memory, having electronically readable control
signals stored thereon, which cooperate (or are capable of cooperating) with a
programmable computer system such that the respective method is performed. Some
embodiments according to the invention comprise a data carrier having electronically
readable control signals, which are capable of cooperating with a programmable computer
system, such that one of the methods described herein is performed. Generally,
embodiments of the present invention can be implemented as a computer program product
with a program code, the program code being operative for performing one of the methods
when the computer program product runs on a computer. The program code may for
example be stored on a machine readable carrier. Other embodiments comprise the
computer program for performing one of the methods described herein, stored on a
machine readable carrier. In other words, an embodiment of the inventive method is,
therefore, a computer program having a program code for performing one of the methods
described herein, when the computer program runs on a computer. A further embodiment
of the inventive methods is, therefore, a data carrier (or a digital storage medium, or a
computer-readable medium) comprising, recorded thereon, the computer program for
performing one of the methods described herein. A further embodiment of the inventive
method is, therefore, a data stream or a sequence of signals representing the computer
program for performing one of the methods described herein. The data stream or the
sequence of signals may for example be configured to be transferred via a data
communication connection, for example via the Internet. A further embodiment comprises
a processing means, for example a computer, or a programmable logic device, configured

to or adapted to perform one of the methods described herein. A further embodiment
comprises a computer having installed thereon the computer program for performing one
of the methods described herein. In some embodiments, a programmable logic device (for
example a field programmable gate array) may be used to perform some or all of the
functionalities of the methods described herein. In some embodiments, a field
programmable gate array may cooperate with a microprocessor in order to perform one of
the methods described herein.

1. Audio encoder for encoding an audio signal, comprising:
a time warper (506);
a time-frequency converter (508) for performing a time/frequency conversion of a
time-warped audio signal into a spectral representation;
a quantizer (512) for quantizing audio values, wherein the quantizer is configured
to quantize to zero audio values below a quantization threshold;
a noise filling calculator (524) for estimating a measure of an energy of audio
values quantized to zero for a time frame of the audio signal to obtain a noise filling
measure; (p. 33,4-12)
an audio signal analyzer (516,520) for analyzing, whether the time frame of the
audio signal has a harmonic or speech characteristic;
a manipulator (602) for manipulating the noise filling measure depending on a
harmonic or a speech characteristic of the audio signal to obtain a manipulated
noise filling measure; and
an output interface (522) for generating an encoded signal for transmission or
storage, the encoded signal comprising the manipulated noise filling measure (530);
wherein the manipulator (602) is configured to apply a normal noise level when the
signal does not have an harmonic or speech characteristic and when no time warp is
applied, and to manipulate the noise filling level to be lower than in the normal case
when a pitch contour as found, which indicates a harmonic content, and the time
warp is active.
2. The audio encoder in accordance with claim 1,

in which the audio signal analyzer (516, 520) comprises a pitch trigger for
generating an indication of a pitch, when a pitch is found in the time frame of the
audio signal, and
in which the manipulator (602) is configured for reducing the noise filling measure,
when a pitch is found.
3. Audio encoder in accordance with claim 1 or 2,
in which the audio signal analyzer comprises a voiced/unvoiced detector (520) for
detecting, whether at least a portion of the time frame is voiced,
in which the manipulator (602) is configured for reducing the noise filling measure
or for zeroing the noise filling measure, when the portion is detected to be voiced,
and
in which the manipulator (602) is configured to not manipulate or to manipulate the
noise filling measure to a smaller degree, when the portion is detected to be
unvoiced.
4. A decoder for decoding an encoded audio signal comprising:
an input interface (539) for processing the encoded audio signal to obtain a noise
filling measure (543) and encoded audio data (546);
a decoder/re-quantizer (547, 550) for generating re-quantized data;
a signal analyzer (600) for retrieving information, whether a time frame of the
audio data has harmonic or speech characteristic; and
a noise filler (552) for generating noise filling audio data,
wherein the noise filler (552) is configured to generate noise filling data in response
to the noise filling measure and the harmonic or speech characteristic of the audio
data; and
a processor (556, 558, 560) for processing the re-quantized data and the noise
filling audio data to obtain a decoded audio signal (564);

wherein the encoded audio signal comprises data (542, 541) indicating, whether the
time frame of the audio data has a harmonic or speech characteristic, and
wherein the signal analyzer (600) is configured for analyzing the encoded audio
signal to retrieve a data indicating, whether the time frame of the audio data has a
harmonic or speech characteristic,
wherein the data is an indication that the time portion has been subjected to a time
warping processing, and
wherein the processor comprises a time dewarper (558) for time dewarping an
audio signal derived from noise filling data and re-quantized data.
5. Method for encoding an audio signal, comprising:
time warping (506) an audio signal;
performing (508) a time/frequency conversion of a time-warped audio signal into a
spectral representation;
quantizing (512) audio values, wherein values below a quantization threshold are
quantized to zero;
estimating (524) a measure of an energy of audio values quantized to zero for a
time frame of the audio signal;
analyzing (516,520), whether the time frame of the audio signal has a harmonic or
speech characteristic;
manipulating (602) the noise filling measure depending on a harmonic or a speech
characteristic of the audio signal to obtain a manipulated noise filling measure such
that a normal noise level is applied when the signal does not have an harmonic or
speech characteristic and when no time warp is applied, and such that the noise
filling level is manipulated to be lower than in the normal case when a pitch
contour as found, which indicates a harmonic content, and the time warp is active;
and

generating (522) an encoded signal for transmission or storage, the encoded signal
comprising the manipulated noise filling measure (530).
6. Method for decoding an encoded audio signal, wherein the encoded audio signal
comprises data (542, 541) indicating, whether the time frame of the audio data has a
harmonic or speech characteristic, comprising:
processing (539) the encoded audio signal to obtain a noise filling measure (543)
and encoded audio data (546);
analyzing the encoded audio signal to retrieve a data indicating, whether the time
frame of the audio data has a harmonic or speech characteristic, wherein the data is
an indication that the time portion has been subjected to a time warping processing;
generating (547, 550) re-quantized data;
retrieving (600) information, whether a time frame of the audio data has harmonic
or speech characteristic; and
generating (552) noise filling audio data in response to the noise filling measure
and the harmonic or speech characteristic of the audio data; and
processing (556, 558, 560) the re-quantized data and the noise filling audio data to
obtain a decoded audio signal (564) wherein the processing comprises time
dewarping an audio signal derived from noise filling data and re-quantized data.
7. Computer program having a program code for performing, when running on a
computer, the method of claim 5 or the method of claim 6.
8. Audio encoder for generating an encoded audio signal, comprising:
an audio signal analyzer (516, 520) for analyzing, whether a time frame of the
audio signal has a harmonic or speech characteristic;
a window function controller (504) for selecting a window function depending on a
harmonic or speech characteristic of the audio signal;

a windower (502) for windowing the audio signal using the selected window
function to obtain a windowed frame; and
a processor (508, 512) for further processing the windowed frame to obtain the
encoded audio signal;
wherein the window function controller (504) comprises a transient detector (700)
for detecting a transient, wherein the window function controller is configured for
switching from a window function for a long block to a window function for a short
block, when a transient is detected and a harmonic or speech characteristic is not
found by the audio signal analyzer (516, 520), and for not switching to the window
function for the short block, when a transient is detected and a harmonic or speech
characteristic is found by the audio signal analyzer (516, 520); and
wherein the window function controller (504) is configured for switching to a
window function (707) being longer than the window function for a short block and
adapted to obtain a shorter left-sided overlap length (712) with a previous window
(706) than the window function (714) for a long block, when a transient is detected
and the signal has a harmonic or speech characteristic, such that the window
function (707) adapted to obtain a shorter overlap length is used for windowing a
speech onset or an onset of a harmonic signal.
9. Audio encoder for generating an encoded audio signal, comprising:
an audio signal analyzer (516, 520) for analyzing, whether a time frame of the
audio signal has a harmonic or speech characteristic;
a window function controller (504) for selecting a window function depending on a
harmonic or speech characteristic of the audio signal;
a windower (502) for windowing the audio signal using the selected window
function to obtain a windowed frame;
a processor (508, 512) for further processing the windowed frame to obtain the
encoded audio signal, and
a transient detector (700);

wherein the transient detector (700) is configured for detecting a quantitative
characteristic of the audio signal and to compare the quantitative characteristic to a
controllable threshold, wherein a transient is detected, when the quantitative
characteristic has a predetermined relation to the controllable threshold, and
wherein the audio signal analyzer is configured for controlling the variable
threshold so that a likelihood for a switch to a window function for a short block is
reduced, when the audio signal analyzer (516, 520) has found a harmonic or speech
characteristic.
10. Method for generating an encoded audio signal, comprising:
analyzing (516, 520), whether a time frame of the audio signal has a harmonic or
speech characteristic;
selecting (504) a window function depending on a harmonic or speech
characteristic of the audio signal;
windowing (502) the audio signal using the selected window function to obtain a
windowed frame; and
processing (508, 512) the windowed frame to obtain the encoded audio signal;
wherein a switching is performed from a window function for a long block to a
window function for a short block, when a transient is detected and a harmonic or
speech characteristic is not found by the analyzing, and
wherein a switching is performed to a window function (707) being longer than the
window function for a short block and having a shorter left-sided overlap (712)
than the window function (714) for a long block, when a transient is detected and
the signal has a harmonic or speech characteristic, such that the window function
(707) having a shorter overlap is used for windowing a speech onset or an onset of
a harmonic signal.
11. Method for generating an encoded audio signal, comprising:
analyzing (516, 520), whether a time frame of the audio signal has a harmonic or
speech characteristic;

selecting (504) a window function depending on a harmonic or speech
characteristic of the audio signal;
windowing (502) the audio signal using the selected window function to obtain a
windowed frame; and
processing (508, 512) the windowed frame to obtain the encoded audio signal;
wherein a quantitative characteristic of the audio signal is detected and the
quantitative characteristic is compared to a controllable threshold, wherein a
transient is detected, when the quantitative characteristic has a predetermined
relation to the controllable threshold; and
wherein the variable threshold is controlled so that a likelihood for a switch to a
window function for a short block is reduced, when a harmonic or speech
characteristic has been found.
12. Computer program having a program code for performing, when running on a
computer, the method of claim 10 or 11.
13. Audio encoder for generating an audio signal, comprising:
a controllable time warper (506) for time warping the audio signal to obtain a time
warped audio signal;
a time/frequency converter (508) for converting at least a portion of the time
warped audio signal into a spectral representation;
a temporal noise shaping stage for performing a prediction filtering over frequency
of the spectral representation in accordance with a temporal noise shaping control
instruction (803), wherein the prediction filtering is not performed, when the
temporal noise shaping control instruction does not exist;
a temporal noise shaping controller (800, 802, 804) for generating the temporal
noise shaping control instruction based on the spectral representation,

wherein the temporal noise shaping controller is configured for increasing a
likelihood for performing the predictive filtering over frequency, when the spectral
representation is based on a time warped audio signal or for decreasing the
likelihood for performing the prediction filtering over frequency, when the spectral
representation is not based on a time warped audio signal; and
a processor (512) for further processing an output of the temporal noise shaping
stage to obtain the encoded audio signal (532);
wherein the temporal noise shaping controller (800, 802, 804) is configured for
estimating a gain in a bitrate or a quality, when the audio signal is subjected to the
prediction filtering by the temporal noise shaping stage (510), for comparing (802)
the estimated gain to a decision threshold, and
for deciding (802), in favor of the prediction filtering, when the estimated gain is in
a predetermined relation to the decision threshold,
wherein the temporal noise shaping controller is furthermore configured for varying
(804) the decision threshold so that, for the same estimated gain, the prediction
filtering is activated, when the spectral representation is based on a time warped
signal, and is not activated, when the spectral representation is not based on a time-
warped audio signal.
14. Audio encoder in accordance with claim 13, in which the time warper comprises a
signal classifier (520) for detecting voiced or unvoiced speech, and
in which the temporal noise shaping controller (800, 802, 804) is configured for
increasing the likelihood, when a voiced speech is detected, or when an unvoiced
speech is detected and the spectral representation is based on the time warped audio
signal.
15. Method for generating an audio signal, comprising:
for time warping (506) the audio signal to obtain a time warped audio signal;
converting (508) at least a portion of the time warped audio signal into a spectral
representation;

performing a prediction filtering over frequency of the spectral representation in
accordance with a temporal noise shaping control instruction (803), wherein the
prediction filtering is not performed, when the temporal noise shaping control
instruction does not exist;
generating (800, 802, 804) the temporal noise shaping control instruction based on
the spectral representation,
wherein a likelihood for performing the predictive filtering over frequency is
increased, when the spectral representation is based on a time warped audio signal
or wherein the likelihood for performing the prediction filtering over frequency is
decreased, when the spectral representation is not based on a non-time-warped
audio signal; and
processing (512) an output of the temporal noise shaping stage to obtain the
encoded audio signal (532);
wherein a gain in a bitrate or a quality, when the audio signal is subjected to the
prediction filtering by the temporal noise shaping stage (510), is estimated, and
wherein the estimated gain is compared to a decision threshold, for deciding (802),
in favor of the prediction filtering, when the estimated gain is in a predetermined
relation to the decision threshold,
wherein the decision threshold is varied so that, for the same estimated gain, the
prediction filtering is activated, when the spectral representation is based on a time
warped signal, and is not activated, when the spectral representation is not based on
a time-warped audio signal..
16. Computer program having a program code for performing, when running on a
computer, the method of claim 15.
17. Audio encoder for encoding an audio signal, comprising:
a time warper (506) for warping an audio signal using a variable time warping
characteristic;

a time/frequency converter (508) for converting a time warped audio signal into a
spectral representation having a number of spectral coefficients; and
a processor (512) for processing a variable number of spectral coefficients to
generate an encoded audio signal,
wherein the processor (512, 1000) is configured for variably setting a number of
spectral coefficients for a frame of the audio signal based on the time warping
characteristic for the frame so that a bandwidth variation represented by the
processed number of frequency coefficients from frame to frame is reduced or
eliminated.
18. Audio encoder in accordance with claim 17,
in which the variable time warping characteristic comprises a local sampling
frequency (fsiO for a frame, and
in which the processor (512, 1000) is configured to increase a number of spectral
coefficients, when the local sampling frequency is increased, or in which the
processor (512, 1000) is configured for decreasing the number of spectral
coefficients, when the local sampling frequency is decreased.
19. Audio encoder in accordance with claim 17 or 18, further comprising a bandwidth
extension encoder for encoding a spectral band above a cross-over frequency
(1200) using parameters derived from a band of the audio signal above the cross-
over frequency (1200), wherein the cross-over frequency is a maximum frequency
of a target bandwidth for each frame.
20. Audio encoder in accordance with claim 19, in which the audio signal, before being
time warped, is sampled using a normal sampling frequency (fN), and in which the
processor (512, 1000) is configured to use a predetermined number of spectral
coefficients (NN) derived from the cross-over frequency and the normal sampling
frequency, when the local sampling frequency is equal to the normal sampling
frequency, or to use a higher number of spectral coefficients compared to the
predetermined number of spectral coefficients (NN), when the local sampling
frequency is higher than the normal sampling frequency (fN), or to use a lower
number compared to the predetermined number of spectral coefficients, when the
local sampling frequency is lower than the normal sampling frequency (fN).

21. Audio encoder in accordance with one of claims 17 to 20,
in which the processor comprises a quantizer for quantizing the spectral coefficients
to obtain quantized spectral coefficients, and an entropy encoder for entropy
encoding the quantized spectral coefficients,
wherein the processor (512, 1000) includes a selector for discarding spectral
coefficients not included in the set number of spectral coefficients before or after
quantizing so that the encoded audio signal only comprises the spectral coefficients,
which have not been discarded, or
wherein the processor includes a selector for adding spectral coefficients required
by the set number of spectral coefficients before or after quantizing so that the
encoded audio signal additionally comprises the added spectral coefficients.
22. Method for encoding an audio signal, comprising:
Time warping (506) an audio signal using a variable time warping characteristic;
converting (508) a time warped audio signal into a spectral representation having a
number of spectral coefficients; and
processing (512) a variable number of spectral coefficients to generate an encoded
audio signal,
wherein a variable number of spectral coefficients for a frame of the audio signal is
set based on the time warping characteristic for the frame so that a bandwidth
variation represented by the processed number of frequency coefficients from frame
to frame is reduced or eliminated.
23. Computer program having a program code for performing, when running on a
computer, the method of claim 22.
24. A time warp activation signal provider (100; 230; 234) for providing a time warp
activation signal (112; 232; 234p) on the basis of a representation (110; 234e; 234k)
of an audio signal, the time warp activation signal provider comprising:

an energy compaction information provider (120; 234f; 2341; 325; 370) configured
to provide an energy compaction information (122; 234m; 234n; 326; 374)
describing a compaction of energy in a time warp transformed spectrum
representation (222) of the audio signal; and
a comparator (130; 234o) configured to compare the energy compaction
information (122; 234m; 234n; 326; 374) with a reference value, and to provide the
time warp activation signal (112; 232; 234p) in dependence on a result of the
comparison.
25. The time warp activation signal provider (100; 230; 234) according to claim 24,
wherein the energy compaction information provider (120; 234f; 2341) is
configured to provide a measure of spectral flatness describing the time warp
transformed spectrum representation (234e; 234k) of the audio signal as the energy
compaction information (122; 234m; 234n).
26. The time warp activation signal provider (100; 230; 234) according to claim 25,
wherein the energy compaction information provider (120; 234f; 2341) is
configured to compute a quotient of a geometric mean of the time warp transformed
power spectrum (234e; 234k) of the audio signal and an arithmetic mean of the time
warp transformed power spectrum (234e; 234k) of the audio signal to obtain the
measure of spectral flatness.
27. The time warp activation signal provider (100; 230; 234) according to one of claims
24 to 26, wherein the energy compaction information provider (120; 234f; 2341) is
configured to emphasize a higher-frequency portion of the time warp transformed
spectrum representation (234e; 234k) when compared to a lower frequency portion
of the time warp transformed spectrum representation (234e; 234k) to obtain the
energy compaction information (122; 234m; 234n).
28. The time warp activation signal provider (100;230; 234) according to one of claims
24 to 27, wherein the energy compaction information provider (120; 234m; 234n) is
configured to obtain a plurality of band-wise measures of spectral flatness, and to
compute an average of the plurality of band-wise measures of spectral flatness to
obtain the energy compaction information (122,234m;234n).
29. The time warp activation signal provider (100;230;234) according to claim 24,
wherein the energy compaction information provider (120;234f;2341;325) is

configured to provide a measure of perceptual entropy (pe) describing the time
warp transformed spectrum representation (234e;234k) of the audio signal as the
energy compaction information (122;234m;234n).
30. The time warp activation signal provider (100; 230; 234; 325) according to claim
29, wherein the energy compaction information provider (120;234f;2341;325) is
configured to compute an estimated number (nl) of non-zero lines for one or more a
scale factor bands of the time warp transformed spectral representation (234e;
234k) of the audio signal on the basis of a form factor information (ffac(n)) of the
scale factor band, and to compute the measure of perceptual entropy (326) for a
scale factor band under consideration using a multiplication of the estimated
number (nl) of non-zero lines and an energy measure of the scale factor band under
consideration.
31. The time warp activation signal provider (100;230;234) according to claim 24,
wherein the energy compaction information provider (120;234f;2341;370) is
configured to provide an autocorrelation measure (374) describing an
autocorrelation of a time warped time domain representation of the audio signal
(234e; 234k) as the energy compaction information.
32. The time warp activation signal provider (100;230;234) according to claim 31,
wherein the energy compaction information provider (120;234f;2341;370) is
configured to determine a sum of absolute values of a normalized autocorrelation
function of the time warped representation (234e;234k) of the audio signal to obtain
the energy compaction information.
33. The time warp activation signal provider (100;230) according to one of claims 24 to
32, wherein the time warp activation signal provider comprises a reference value
calculator configured to compute the reference value on the basis of an unwarped
spectrum representation of the audio signal (210) or on the basis of an unwarped
time domain representation of the audio signal (210); and
wherein the comparator is configured to form a ratio value using the energy
compaction information (122) describing a compaction of energy in a time warp
transformed spectrum representation of the audio signal and the reference value,
and to compare the ratio value with one or more threshold values to obtain the time
warp activation signal as the result of the comparison.

34. The time warp activation signal provider (230;234) according to one of the claims
24 to 32, wherein the time warp activation signal provider comprises a reference
value calculator configured to compute the reference value on the basis of a time
warped representation of the input signal (210), time warped using a standard time
warp contour information (288); and
wherein the comparator is configured to form a ratio value using the energy
compaction information (234e) describing a compaction of energy in a time warped
representation of the audio signal and the reference value, and to compare the ratio
value with one or more threshold values to obtain the time warp activation signal as
the result of the comparison.
35. An audio signal encoder (200) for encoding an input audio signal (210) to obtain an
encoded representation (212) of the input audio signal, the audio signal encoder
comprising:
a time warp transformer (220) configured to provide a time warp transformed
spectral representation (222) on the basis of the input audio signal (210) using a
time warp contour;
a time warp activation signal provider (100; 230; 234) according to one of claims
24 to 34 wherein the time warp activation signal provider is configured to receive
the input audio signal (210) and to provide the time warp activation signal (112;
232; 234p);and
a controller (240) configured to selectively provide, in dependence on the time
warp activation signal (112; 232; 234p), a newly found time warp contour
information (286), describing a non-constant time warp contour portion, or a
standard time warp contour information (288), describing a constant time warp
contour portion, to the time warp transformer (220) to describe the time warp
contour used by the time warp transformer (220).
36. The audio signal encoder according to claim 35, wherein the audio signal encoder
comprises an output interface (280) configured to include the time warp
transformed spectral representation (222) into the encoded representation (212) of
the audio signal, and

to selectively include, in dependence on the time warp activation signal (232), a
time warp contour information into the encoded representation (212) of the audio
signal.
37. A method (400) for providing a time warp activation signal on the basis of an audio
signal, the method comprising:
providing (410) an energy compaction information describing a compaction of
energy in a time warp transformed spectral representation of the audio signal;
comparing (420) the energy compaction information with a reference value; and
providing (430) the time warp activation signal in dependence on the result of the
comparison.
38. A method (450) for encoding an input audio signal to obtain an encoded
representation of the input audio signal, the method comprising:
providing (470) a time warp activation signal according to claim 37, wherein the
energy compaction information describes a compaction of energy in a time warp
transformed spectrum representation of the input audio signal; and
selectively providing (480), in dependence on the time warp activation signal, a
description of the time warp transformed spectral representation of the input audio
signal or description of a non-time-warp-transformed spectral representation of the
input audio signal for inclusion into the encoded representation of the input audio
signal.
39. A computer program for performing the method of claim 37 or 38 when the
computer program runs on the computer.

An audio encoder comprises a window function controller (504), a windower (502), a time warper (506) with a final quality check functionality, a time/frequency converter (508), a TNS stage (510) or a quantizer encoder (512), the window function controller (504), the time warper (506), the TNS stage (510) or an additional noise filling analyzer (524) are controlled by signal analysis results obtained by a time warp analyzer (516) or a signal classifier (520). Furthermore, a decoder applies a noise filling operation using a manipulated noise filling estimate depending on a harmonic or speech characteristic of the audio signal.